method for transmitting uplink data in wireless communication system and device to the same

专利摘要:
it is a method for transmitting a shared physical uplink channel (pusch) performed by a user's equipment (eu) in a wireless communication system that may include receiving downlink control information (dci) for programming transmission of uplink (ul); and perform pusch transmission based on a dictionary of codes based on the pre-coding information included in the dci.
公开号:BR112019020385A2
申请号:R112019020385
申请日:2018-04-02
公开日:2020-04-22
发明作者:Park Haewook；Kim Hyungtae；Kang Jiwon；Park Jonghyun；Kim Kijun
申请人:Lg Electronics Inc；
IPC主号:

专利说明:

"METHOD FOR TRANSMITING UPLINK DATA IN WIRELESS COMMUNICATION SYSTEM AND APPLIANCE FOR THE SAME" [Technical Field] [001] The present invention is related to wireless communications, and, more specifically, to a method to transmit uplink data performed User Equipment and a device to perform / support it.
[Background of the Invention] [002] Mobile communication devices were developed to offer voice services, while guaranteeing user activity. However, the service coverage of mobile communication systems has even extended to data services, as well as voice services, and today an abrupt increase in traffic has resulted in a shortage of resources and demand for high-speed services by user, taking advanced mobile communication systems necessary.
[003] The requirements of the next generation mobile communication system may include supporting immense data traffic, a notable increase in the transfer rate of each user, the accommodation of a considerably greater number of connection devices, very low data latency. end to end, and high energy efficiency. To that end, several techniques, such as small cell enhancement, dual connectivity, massive Multiple Inputs (MIMO), full duplex within the operating band, non-orthogonal multiple access (NOMA), super-wide support band, and network communication of devices has been developed.
[Disclosure] [Technical Problem] [004] One method of the present invention is to propose a method of operating UL data transmission from User Equipment based
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2/129 in a code dictionary.
[005] In addition, an objective of the present invention is to propose a diversified / efficient code dictionary recently based on the CPOFDM waveform.
[006] The technical objectives that will be achieved in the present invention are not limited to the technical objects described above, and other technical objects that are not described here will become apparent to those skilled in the art based on the following description.
[Technical Solution] [007] According to one aspect of the present invention, a method for transmitting a Shared Physical Uplink Channel (PUSCH) based on a code dictionary performed by a User Equipment (UE) on a wireless communication system may include receiving downlink control information (DCI) for uplink transmission programming (UL); and carry out PUSCH transmission based on code dictionary based on the pre-coding information included in the DCI, when PUSCH is transmitted using four antenna ports, the code dictionary including: a first group including non-coherent pre-coding arrays to select only one port for each layer, a second group including partial coherence pre-coding matrices for selecting two ports on at least one layer, and a third group including full coherence pre-coding matrices for selection of all doors for each of the layers.
[008] In addition, the non-coherent pre-coding matrix can be a matrix including a non-zero vector in each column, the partial coherent pre-coding matrix can be a matrix including two vectors with a different value of zero in at least one column, and the total coherence precoding matrix can be a matrix including only vectors with different values
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3/129 of zero.
[009] In addition, the code dictionary can be a code dictionary based on the Division Multiplexing waveform in Cyclic Prefix Orthogonal Frequencies (CP-OFDM).
[010] In addition, the DCI may include the Transmitted Pre-Coding Matrix Indicator (TPMI), which is the information from an index of the pre-coding matrix selected for the transmission of PlISCH as the pre-coding information.
[011] In addition, the TPMI can be encoded together with the Degree Indicator (IR), which is the layer information used in the transmission of PlISCH.
[012] In addition, TPMI can be indicated for each Sounding Reference Signal (SRS) resource configured for the UE, and where IR is generally indicated for configured SRS resources.
[013] In addition, TPMI and IR can generally be indicated for all SRS resources configured for the UE.
[014] In addition, TPMI and RI can be indicated for each SRS resource configured for the UE.
[015] In addition, the DMRS field size predefined in the DCI for a given DMRS port can be determined differently according to the RI coded in conjunction with the TPMI.
[016] In addition, the method for transmitting PUSCH can additionally include receiving restriction information from a series of layers usable in PUSCH transmission.
[017] In addition, the size of a field in which the TPMI and the RI are encoded together can be decided based on the restriction information on the number of layers.
[018] In addition, the method for transmitting PUSCH may additionally include receiving restriction information from the pre-coding matrix usable in
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4/129 PUSCH transmission in the code dictionary.
[019] In addition, the pre-coding matrix restriction information may indicate the pre-coding matrix usable in transmitting PUSCH in the group unit or in the individual pre-coding matrix unit.
[020] In addition, the size of a field in which the TPMI and the RI are coded together can be decided based on the restriction information from the pre-coding matrix.
[021] In addition, according to another aspect of the present invention, user equipment (UE) for transmitting a Shared Physical Uplink Channel (PUSCH) based on a code dictionary in a wireless communication system may include a radio frequency (RF) to transmit and receive a radio signal; and a processor to control the RF unit, the processor is configured to perform: reception of downlink control information (DCI) for uplink transmission programming (UL); and perform PUSCH transmission based on code dictionary based on the pre-coding information included in the DCI, when PUSCH is transmitted using four antenna ports, the code dictionary including: a first group including non-coherent pre-coding matrices for select only one port for each layer, a second group including partial coherence pre-coding matrices for selection of two ports on at least one layer, and a third group including full coherence pre-coding matrices for selection of all ports for each of the layers.
[Technical Effects] [022] In accordance with the present invention, there is an effect that the code dictionary-based UL data transmission operation can be efficiently supported in a new wireless communication system.
[023] In addition, according to the present invention, there is an effect that
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5/129 a new UL code dictionary is used, which is available to support various transmission operations (non-coherent transmission operation, partial coherence transmission operation, full coherence transmission operation, etc.).
[024] It will be appreciated by those skilled in the art that the effects that can be achieved through the present disclosure are not limited to what has been described particularly here before, and other advantages of the present invention will be understood more clearly from the following detailed description.
[Description of Drawings] [025] The accompanying drawings, which are included here as part of the description to assist in the understanding of the present invention, provide modalities of the present invention, and describe the technical aspects of the present invention with the description below.
[026] FIG. 1 illustrates the structure of a radio frame in a wireless communication system to which the present invention can be applied.
[027] FIG. 2 is a diagram illustrating a resource grid for a downlink segment in a wireless communication system to which the present invention can be applied.
[028] FIG. 3 illustrates a downlink subframe structure in a wireless communication system to which the present invention can be applied.
[029] FIG. 4 illustrates an uplink subframe structure in a wireless communication system to which the present invention can be applied.
[030] FIG. 5 shows the configuration of a known MIMO communication system.
[031] FIG. 6 is a diagram illustrating a channel from a plurality of transmitting antennas to a single receiving antenna.
[032] FIG. 7 illustrates a 2D AAS having 64 antenna elements in one
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6/129 wireless communication system to which the present invention is applicable.
[033] FIG. 8 illustrates a system in which an eNB or UE has a plurality of transmit / receive antennas capable of forming AAS-based 3D beams in a wireless communication system to which the present invention is applicable.
[034] FIG 9 illustrates a 2D antenna system having cross polarization in a wireless communication system to which the present invention is applicable.
[035] FIG 10 illustrates models of transceiver unit in a wireless communication system to which the present invention is applicable.
[036] FIG. 11 illustrates an autonomous subframe structure to which the present invention can be applied.
[037] FIG. 12 is a diagram schematically illustrating a hybrid beam forming structure in the aspect of a TXRU and a physical antenna.
[038] FIG. 13 is a diagram schematically illustrating a synchronization signal in the DL transmission process and a beam scan operation for system information.
[039] FIG. 14 illustrates an array of panel antennas to which the present invention can be applied.
[040] FIG. 15 illustrates a schematic UL data transmission process between a UE and a gNB that can be applied to the present invention.
[041] FIG. 16 is a diagram illustrating the allocation of TPMI SB according to an embodiment of the present invention.
[042] FIG. 17 is a flow chart illustrating the PUSCH transmission operation of a UE in accordance with an embodiment of the present invention.
[043] FIG. 18 is a block diagram of a wireless communication device according to an embodiment of the present invention.
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7/129 [044] FIG. 19 is a diagram illustrating an example of an RF module of a wireless communication device to which the method proposed in the present disclosure can be applied.
[045] FIG. 20 is a diagram illustrating another example of an RF module of a wireless communication device to which the method proposed in the present disclosure can be applied.
[Best Mode for the Invention] [046] Some preferred embodiments of the present invention are described in detail with reference to the accompanying drawings. A detailed description to be disclosed along with the accompanying drawings is intended to describe some embodiments of the present invention and is not intended to describe a single embodiment of the present invention. The following detailed description includes more details to provide an in-depth understanding of the present revelation. However, those skilled in the art will understand that the present invention can be implemented without such additional details.
[047] In some cases, in order to prevent the concept of the present invention from becoming vague, known structures and devices are omitted or can be illustrated in the form of a block diagram based on the essential functions of each structure and device.
[048] In this specification, a base station has the meaning of a terminal node in a network through which the base station communicates directly with a device. In this document, a specific operation that is described to be performed by a base station can be performed by an upper node of the base station according to the circumstances. That is, it is evident that in a network including a plurality of network nodes including a base station, various operations performed for communication with a device can be performed by the base station or other network nodes in addition to the base station. The base station
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8/129 (BS) can be replaced by another term, such as fixed station, Node B, eNB (evolved NodeB), Base Transceiver System (BTS), access point (AP), or gNB (Next Generation NodeB) . In addition, the device can be fixed or mobile, and can be replaced by another term, such as User Equipment (UE), Mobile Station (MS), User Terminal (UT), Subscriber Mobile Station (MSS), Subscriber Station (SS), Advanced Mobile Station (AMS), Wireless Terminal (WT), Machine Type Communication Device (MTC), Machine to Machine Device (M2M), or Device to Device Type Device (D2D ).
[049] Hereinafter, “downlink” (DL) refers to communication from an eNB to the UE, and uplink (UL) refers to communication from the UE to an eNB. In the DL, a transmitter can be part of an eNB, and a receiver can be part of the UE. In UL, a transmitter can be part of the UE, and a receiver can be part of an eNB.
[050] The specific terms used in the description below have been presented to assist in the understanding of the present invention, and the use of such specific terms can be modified in several ways without departing from the technical spirit of the present invention.
[051] The following technologies can be used in a variety of wireless communication systems, such as Code Division Multiple Access (CDMA), Frequency Division Multiple Access (FDMA), Time Division Multiple Access (TDMA) Orthogonal Frequency Division Multiple Access (OFDMA), Single Carrier Frequency Division Multiple Access (SCFDMA) and Non-Orthogonal Multiple Access (NOMA). CDMA can be implemented using radio technology, such as Universal Land Radio Access (UTRA) or CDMA2000. TDMA can be implemented using radio technology, such as a Global System for Mobile Communications (GSM) / Service
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9/129
General Radio Package (GPRS) I Enhanced Data Rate for GSM Evolution (EDGE). OFDMA can be implemented using radio technology, such as the Institute of Electrical and Electronics Engineers (IEEE) 802.11 (Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802.20, or UTRA Evolved (E-UTRA). UTRA is part of a Universal Mobile Telecommunications System (UMTS). The 3rd Generation Partnership Project (3GPP) Long Term Evolution (LTE) is part of an Evolved UMTS (E-UMTS) using Land Access via Evolved UMTS Radio (E-UTRA), and adopts OFDMA in the downlink and adopts SC-FDMA on the uplink. Advanced LTE (ΙΤΕΑ) is the evolution of LTE 3GPP.
[052] The modalities of the present invention can be supported by the standard documents revealed in at least one of the IEEE 802, 3GPP and 3GPP2, that is, radio access systems. That is, the steps or parts that belong to the modalities of the present invention and that are not described in a way that clearly exposes the technical spirit of the present invention can be supported by the documents. In addition, all terms disclosed in this document can be described by standard documents.
[053] In order to clarify the description better, the 3GPP LTE / LTE-A / 5G is briefly described, but the technical characteristics of the present invention are not limited to it.
General system to which the present invention can be applied [054] FIG. 1 shows the structure of a radio frame in a wireless communication system to which a modality of the present invention can be applied.
[055] The 3GPP LTE / LTE-A supports a type 1 radio frame structure that may be applicable to Frequency Division Duplexing (FDD) and a radio frame structure that may be applicable to Time Division Duplexing (TDD).
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10/129 [056] The size of a radio frame in the time domain is represented as a multiple of a time unit of T_s = 1 / (15000 * 2048). A UL and DL transmission includes the radio frame with a duration of T_f = 307200 * T_s = 10ms.
[057] FIG. 1 (a) exemplifies a type 1 radio frame structure. The type 1 radio frame can be applied to both the FDD full duplex and the FDD half duplex.
[058] A radio board includes 10 subframes. A radio frame includes 20 segments of duration T_slot = 15360 * T_s = 0.5 ms, and 0 to 19 indexes are provided for each segment. A subframe includes two consecutive time domain segments, and subframe i includes segment 2i and segment 2i + 1. The time required to transmit a subframe is called the Transmission Time Interval (TTI). For example, the duration of subframe i can be 1 ms and the duration of a segment can be 0.5 ms.
[059] A UL transmission and a DL I transmission from the FDD are distinguished in the frequency domain. Although there is no restriction on the full duplex FDD, a UE may not transmit and receive simultaneously in the half duplex FDD operation.
[060] A segment includes a plurality of Orthogonal Frequency Division Multiplexing (OFDM) symbols in the time domain and includes a plurality of Resource Blocks (RBs) in a frequency domain. In LTE 3GPP, OFDM symbols are used to represent a symbol period since OFDMA is used in the downlink. An OFDM symbol can be called an SC-FDMA symbol or symbol period. An RB is a unit of resource allocation and includes a plurality of contiguous subcarriers in a segment.
[061] FIG. 1 (b) shows the type 2 frame structure.
[062] A type 2 radio structure includes two semi-frames, each lasting 153600 * T_s = 5ms. Each semi-frame includes 5 sub-frames of duration
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12/119
30720 * T_s = 1ms.
[063] In the type 2 frame structure of a TDD system, an uplink-downlink configuration is a rule indicating whether the uplink and downlink are allocated (or reserved) for all subframes.
[064] Table 1 shows the uplink-downlink configuration.
[Table 1] ________________________________________________
Uplink-downlink configuration Frequency of Downlink Switching Point for Uplink Subframe number 0 1 2 3 4 5 6 7 8 9 0 5ms D s U U U D s U U U 1 5ms D s U U D D s U U D 2 5ms D s U D D D s u D D 3 10ms D s u U U D D D D D 4 10ms D s u U D D D D D D 5 10ms D s u D D D D D D D 6 5ms D s u U U D s U U D
[065] Referring to Table 1, in each subframe of the radio frame, 'D' represents a subframe for a DL transmission, 'U' represents a subframe for UL transmission, and S ”represents a special subframe including three field types including three field types including a Downlink Pilot Time Segment (DwPTS), a Guard Period (GP), and a Uplink Pilot Time Segment (UpPTS).
[066] A DwPTS is used for initial cell search, synchronization or channel estimation in a UE. An UpPTS is used for channel estimation in an eNB and for synchronizing a UE transmission UL synchronization. A GP is the duration to remove the interference that has occurred on a UL due to the multipath delay of a DL signal between a UL and a DL.
[067] Each subframe i includes segment 2i and segment 2i + 1 of T_slot = 15360 * T_s = 0.5ms.
[068] The UL-DL configuration can be classified into 7 types, and the position and / or the number of a DL subframe, a special subframe and a subframe of
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UL are different for each configuration.
[069] Table 2 represents the configuration (DwPTS / GP / UpPTS duration) of a special subframe.
[Table 2] ________
Special subframe configuration Normal cyclic prefix in the downlink Cyclic prefix extended in the downlink DwPTS UpPTS DwPTS UpPTSNormal cyclic prefix on the uplink Cyclic prefix extended on uplinkNormal cyclic prefix on the uplink Cyclic prefix extended on uplink 0 6592 -T _s 2192-T _s 2560 -T _s 7680 -T _s 2192-T _s 2560 -T _s 1 19760 -T _s 20480 -T _s 2 21952-Tj 23040 -T _s 3 24144-7 _S 25600 -T _s 4 26336-Tj 7680 -T _s 4384-Tj 5120-T _s 5 6592-Tj 4384-7 _s 5120-7 _s 20480 -T _s 6 19760 -T _s 23040 -T _s 7 21952-Tj - - - 8 24144-7 _S - - -
[070] The structure of a radio subframe according to the example of
FIG. 1 is just an example, and the number of subcarriers included in a radio frame, the number of segments included in a subframe and the number of OFDM symbols included in a segment can be changed in several ways.
[071] FIG. 2 is a diagram illustrating a resource grid for a downlink segment in a wireless communication system to which a modality of the present invention can be applied.
[072] Referring to FIG. 2, a downlink segment includes a plurality of OFDM symbols in a time domain. It is described here that a downlink segment includes 7 OFDMA symbols and a resource block includes 12 subcarriers for illustrative purposes only, and the present invention is not limited to this.
[073] Each element in the resource grid is called an element of
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13/129 resource, and a resource block (RB) includes 12x7 resource elements. The number of N ^A DL RBs included in a downlink segment depends on a downlink transmission bandwidth.
[074] The structure of an uplink segment can be the same as that of a downlink segment.
[075] FIG. 3 shows the structure of a downlink subframe in a wireless communication system to which a modality of the present invention can be applied.
[076] Referring to FIG. 3, a maximum of three OFDM symbols located at the front of a first segment of a subframe corresponds to a control region in which control channels are allocated, and the remaining OFDM symbols correspond to a data region in which a physical channel shared downlink (PDSCH) is allocated. The downlink control channels used in LTE 3GPP include, for example, a physical control format indicator channel (PCFICH), a physical downlink control channel (PDCCH), and a hybrid ARQ indicator physical channel (PHICH).
[077] A PCFICH is transmitted in the first OFDM symbol of a subframe and carries information about the number of OFDM symbols (that is, the size of a control region) that is used to transmit control channels within the subframe. A PHICH is a response channel for uplink and carries a recognition (ACK) / non-recognition (NACK) signal to an Automatic Hybrid Replay Request (HARQ). The control information transmitted in a PDCCH is called Downlink Control Information (DCI). The DCI includes uplink resource allocation information, downlink resource allocation information, or an uplink transmit power control command (Tx) for a specific UE group.
[078] FIG. 4 shows the structure of an uplink subframe in a system
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14/129 wireless communication to which a modality of the present invention can be applied.
[079] Referring to FIG. 4, the uplink subframe can be divided into a control region and a data region in a frequency domain. A physical uplink control channel (PUCCH) carrying uplink control information is allocated to the control region. A shared physical uplink channel (PUSCH) carrying user data is allocated to the data region. In order to maintain the unique carrier characteristic, a UE does not send a PUCCH and a PUSCH at the same time.
[080] A pair of Resource Blocks (RB) is allocated to a PUCCH for a UE within a subframe. The RBs belonging to a pair of RB occupy different subcarriers in each of the 2 segments. This is called for a pair of RBs allocated to a PUCCH to be skipped in frequency at a segment limit.
Multiple Inputs Multiple Outputs (MIMO) MIMO (Multi-Input Multi-Output) [081] A MIMO technology does not use the single transmit antenna and single receive antenna that were normally used until then, but uses a multiple transmit antenna (Tx ) and a multiple reception antenna (Rx). In other words, MIMO technology is a technology to increase capacity or increase performance using multiple input / output antennas at the transmitting or receiving terminal of a wireless communication system. Henceforth, MIMO is called a “multiple input / output antenna”.
[082] More specifically, the multi-input / output antenna technology does not depend on a single antenna path in order to receive a single total message and complete the total data by collecting a plurality of pieces of data received via multiple antennas. As
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15/129 result, the multiple input / output antenna technology can increase a data transfer rate within a specific range of the system and can also increase a range of the system through a specific data transfer rate.
[083] An efficient multi-input / output antenna technology is expected to be used, since next generation mobile communication requires a data transfer rate much higher than that of existing mobile communication. In such a situation, MIMO communication technology is a next generation mobile communication technology that can be widely used in the mobile communication UE and a relay node and has been in evidence as a technology that can overcome a throughput limit. another mobile communication that can be attributed to the expansion of data communication.
[084] Meanwhile, the multi-input / output antenna (MIMO) technology of various transmission efficiency enhancement technologies that are being developed has been in evidence as a method capable of considerably improving the communication capacity and performance of transmission / reception even without the allocation of additional frequencies or an increase in power.
[085] FIG. 5 shows the configuration of a known MIMO communication system.
[086] Referring to FIG. 5, if the number of transmit antennas (Tx) is increased to N_T and the number of receive antennas (Rx) is increased to N_R at the same time, a theoretical channel transmission capacity is increased in proportion to the number of antennas, different from the case where a plurality of antennas is used only on a transmitter or receiver. Therefore, a throughput can be improved, and the efficiency of
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16/129 frequency can be increased considerably. In this case, a transfer rate according to an increase in channel transmission capacity can be theoretically increased by a value obtained by multiplying the next rate increment R_i by a maximum transfer rate R_o if an antenna is used.
[Equation 1]
R _È = min (AÇ, 7V _R ) [087] That is, in a MIMO communication system using 4 transmit antennas and 4 receive antennas, for example, a quadruple transfer rate can be obtained theoretically compared to a single antenna.
[088] Such multi-input / output antenna technology can be divided into a spatial diversity method to increase transmission reliability using symbols that pass through the various channel paths and a spatial multiplexing method to improve a transfer rate by means of sending a plurality of data symbols at the same time using a plurality of transmission antennas. Additionally, active research has recently been carried out to develop a method to appropriately obtain the advantages of the two methods by combining the two methods.
[089] Each method is described in more detail below.
[090] First, the spatial diversity method includes a space-time series code method and a space-time Trelis code series method using a diversity gain and a coding gain at the same time. In general, the Trelis code series method is better in terms of bit error rate enhancing performance and the degree of freedom of code generation, whereas the block code time method in space-time has low complexity operational. Such a gain in spatial diversity
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17/129 can correspond to a quantity corresponding to the product (N_T χ N_R) of the number of transmitting antennas (N_T) and the number of receiving antennas (N_R).
[091] Second, the spatial multiplexing scheme is a method for sending different data streams across transmission antennas. In this case, in a receiver, mutual interference is generated between the data transmitted by a transmitter at the same time. The receiver removes the interference using an appropriate signal processing scheme and receives the data. A noise removal method used in this case may include a Maximum Likelihood Detection (MLD) receiver, a Forcing Zero receiver (ZF), a Minimum Minimum Square Error (MMSE) receiver, Diagonal-Bell Laboratories Layered SpaceTime (D -BLAST) and Vertical-Bell Laboratories Layered Space-Time (V-BLAST). More specifically, if a transmission terminal can be aware of the channel information, a Singular Value Decomposition (SVD) method can be used.
[092] Third, there is a method that uses a combination of spatial diversity and spatial multiplexing. If only a spatial diversity gain needs to be obtained, a performance improvement gain in line with an increase in the diversity gap is gradually saturated. If only a spatial multiplexing gain is used, the transmission reliability on a radio channel is deteriorated. Methods to solve the problems and obtain both gains have been researched and may include a method of transmission diversity in double space-time (double STTD) and a coded modulation with interlacing bits in space-time (STBICM).
[093] In order to describe a communication method in a multiple input / output antenna system, as described above, in more detail, the communication method can be represented as follows through
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12/189 mathematical modeling.
[094] First, as illustrated in FIG. 5, it is assumed that N_T transmitting antennas and NR receiving antennas are present.
[095] First, a transmission signal is described below. If the N_T transmission antennas are present as described above, a maximum number of information units that can be transmitted is N_T, which can be represented using the following vector.
[Equation 2]
S -, 5 ₂ , · · ·, S _N _ [096] Meanwhile, the transmission power may be different in each of the transmission information units s_1, s_2, s_NT. In this case, if the transmission power units are P_1, P_2, P_NT, the transmission information having controlled transmission power can be represented using the following vector.
[Equation 3]
S = [^, ^ 2, ·, ^^ ⁼ [097] Additionally, the transmission information having controlled transmission power in Equation 3 can be represented as follows using the transmission power diagonal matrix P.
[Equation 4]
[098] Meanwhile, the information vector having controlled transmission power in Equation 4 is multiplied by a weight matrix W, thus forming N_T transmission signals x_1, x_2, x_NT that are actually transmitted. In this case, the weight matrix works in order to distribute
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19/129 appropriately the transmission information for the antennas according to a condition of the transport channel. The following can be represented using the transmission signals x_1, x_2, x_NT.
[Equation 5]X1Ί |- x ₂ ’Ll ’22 · - ^W 2N _TX = X, - ^W .2 · - ^W , N _T = Ws = WPs ^X N _T _ ^W N _T ! ^W N _T 2 · ^W N _T N _T _ ^ N _T
[099] In this case, w_ij indicates the weight between the i-th transmission antenna and the j-th transmission information, and W is an expression of a weight matrix. Such a matrix W is called a weight matrix or pre-coding matrix.
[0100] Meanwhile, the transmission signal x, as described above, can be considered to be used in a case where spatial diversity is used and in a case where spatial multiplexing is used.
[0101] If spatial multiplexing is used, all elements of the information vector s have different values, since different signals are multiplexed and transmitted. On the other hand, if spatial diversity is used, all elements of the information vector s have the same value, since the same signals are transmitted through several channel paths.
[0102] A method for mixing spatial multiplexing and spatial diversity can be considered. In other words, the same signals can be transmitted using spatial diversity through 3 transmission antennas, for example, and the remaining different signals can be multiplexed and transmitted spatially.
[0103] If N_R receiving antennas are present, the receiving signals y_1, y_2, y_NR of the respective antennas are represented as follows using a vector y.
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20/129 [Equation 6] y = [51.5 ₂ , ---, 5 ^ f [0104] Meanwhile, if the channels in a multiple input / output antenna communication system are modeled, the channels can be classified according to the transmission / reception antenna indices. A channel passing through a receiving antenna would depart from a transmitting antenna is already represented as h_ij. In this case, it should be noted that, in the order of the h_ij index, the index of a receiving antenna comes first and the index of a transmitting antenna comes next.
[0105] Several channels can be grouped and expressed in a vector and matrix form. For example, a vector expression is described below.
[0106] FIG. 6 is a diagram illustrating a channel from a plurality of transmitting antennas to a single receiving antenna.
[0107] As shown in FIG. 6, a total channel of N_T transmitting antennas to a receiving antenna i can be represented as follows.
[Equation 7]
K ^- [fyl A2, ''] [0108] Additionally, if all channels from the N_T transmitting antenna to NR receiving antennas are represented using a matrix expression, such as Equation 7, they can be represented as follows.
[Equation 8]
hf ΊAn The _i2 Kn _t hjA ₂ i A ₂₂ ^ 2N _T H == ^ 1 The _t2 kjN _T .¾ ¹ Ap ^h N _R N _T _
[0109] Meanwhile, Additive White Noise Gaussian (AWGN) is added
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21/129 to a real channel after the real channel passes through the H channel matrix. Therefore, the AWGN n_1, n_2, ..., n_NR added to the N_R receiving antennas, respectively, are represented using a vector as follows.
[Equation 9] n = [0110] A transmit signal, a receive signal, a channel and the AWGN in a multiple input / output antenna communication system can be represented to have the following relationship by modeling the signal. transmission, reception signal, channel and AWGN, such as those described above.
[Equation 10] / Zj!
^ 21 / z _í2 = Hx + n .¾ [0111] Meanwhile, the number of rows and columns of the H channel matrix indicative of the status of the channels is determined by the number of transmit / receive antennas. In the H channel matrix, as described above, the number of lines becomes equal to the number of receiving antennas N_R, and the number of columns becomes equal to the number of transmitting antennas N_T. That is, the H channel matrix becomes an N_RxN_T matrix.
[0112] In general, the rank (rank) of a matrix is defined as a minimum number of the number of independent rows or columns. Therefore, the degree of the matrix is not greater than the number of rows or columns. As for the style shown, for example, the H degree of the H channel matrix is limited as follows.
[Equation 11] ran] ^ <vú (N _T , N ^
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22/129 [0113] Additionally, if a matrix is subject to eigenvalue decomposition, a degree can be defined as the number of eigenvalues that belong to the eigenvalues and are not equal to 0. Similarly, if a degree is subject to Singular Value Decomposition (SVD), it can be defined as the number of singular values other than 0. Therefore, it can be said that the physical meaning of a degree in a channel matrix is the maximum number in which different information can be be transmitted on a given channel.
[0114] In this specification, a “grade” for MIMO transmission indicates the number of paths through which signals can be transmitted independently at a specific time point and at a specific frequency resource. The “number of layers” indicates the number of signal streams transmitted through each path. In general, a degree has the same meaning as the number of layers, unless otherwise stated, as a transmission terminal sends the number of layers corresponding to the number of degrees used in signal transmission.
Reference signal (RS) [0115] In a wireless communication system, a signal can be distorted during transmission, since data is transmitted over a radio channel. In order for a receiving terminal to receive a precisely distorted signal, the distortion of a received signal needs to be corrected using channel information. In order to detect the channel information, a method is mainly used to detect the channel information using the degree of distortion of a signal transmission method and a signal known both by the transmitting side and the receiving side when they are transmitted through a channel. The aforementioned signal is called a pilot signal or reference signal (RS).
[0116] Even more recently, when most information systems
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23/129 mobile communication transmits a packet, they use a method capable of improving the efficiency of transmitting / receiving data by adopting multiple transmitting antennas and multiple receiving antennas, instead of using a transmitting antenna and an antenna used to date. When data is transmitted and received using multiple input / output antennas, a channel state between the transmitting antenna and the receiving antenna must be detected in order to receive the signal accurately. Therefore, each transmission antenna must have an individual reference signal.
[0117] In a mobile communication system, an RS can basically be divided into two types, depending on its purpose. There is an RS for the purpose of obtaining channel status information and an RS used for data demodulation. The first has the objective of obtaining, by a UE, channel status information in the downlink. Therefore, a corresponding RS must be transmitted over a wide band, and a UE must be able to receive and measure the RS, although the UE does not receive downlink data in a specific subframe. In addition, the former is also used for measurement of radio resource management (RRM), such as handover. The latter is an RS transmitted along with corresponding resources when an eNB transmits the downlink. A UE can perform channel estimation upon receipt of a corresponding RS, and thus can demodulate data. The corresponding RS must be transmitted in a region where the data is transmitted.
[0118] A downlink RS includes a common RS (CRS) for the acquisition of information about a channel state shared by all UEs within a cell and measurement, such as transfer between cells, and a dedicated RS (DRS) used for demodulation of data for only one specific UE. Information for demodulation and channel measurement can be provided using such
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RSs. That is, DRS is used only for data demodulation, and CRS is used for both channel information acquisition and data demodulation objects.
[0119] The receiving side (that is, the UE) measures a channel state based on a CRS and feeds an indicator related to channel quality, such as a channel quality indicator (CQI), a matrix index of pre-coding (PMI) and / or a degree indicator (RI), back to the transmission side (ie, an eNB). CRS is also called cell-specific RS. In contrast, a reference signal related to the return of channel status information (CSI) can be defined as a CSI-RS.
[0120] DRS can be transmitted via resource elements if the data in a PDSCH needs to be demodulated. A UE can receive information about whether a DRS is present through an upper layer, and the DRS is only valid if a corresponding PDSCH has been mapped. DRS can also be called the UE-specific RS or demodulation RS (DMRS).
CSI-RS configuration [0121] In the current LTE standard, the parameters for a CSIRS configuration include antennaPortsCount, subframeConfig, resourceConfig, among others. These parameters indicate the number of antenna ports through which a CSIRS is transmitted, a period and offset from a subframe in which a CSI-RS will be transmitted, the location (that is, an OFDM frequency and symbol index) of the Element Resource (RE) in which a CSI-RS is transmitted in a corresponding subframe, and so on. Specifically, an eNB forwards parameter / information of the following contents when indicating / forwarding a specific CSI-RS configuration to a UE.
[0122] antennaPortsCount: Parameter representing the number of antenna ports used for transmitting the CSI reference signals (for example, 1
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25/129 CSI-RS port, 2 CSI-RS ports, 4 CSI-RS ports or 8 CSI-RS ports).
[0123] - resourceConfig: Parameter in relation to a CSI-RS allocation resource location [0124] - subframeConfig: Parameter in relation to a period and deviation of a subframe in which a CSI-RS will be transmitted [0125] - pc: With respect to the UE's premise on the transmitted power from the reference PDSCH to CSI-CSI return, Pc is the assumed ratio of PDSCH EPRE to CSI-RS EPRE when the UE derives the return from CSI and obtains values in the [-8, 15] dB range with 1 dB step size.
[0126] - zeroTxPowerResourceConfigList: Parameter in relation to a zero power CSIRS.
[0127] - zeroTxPowerSubframeConfig: Parameter in relation to a period and a deviation from a subframe in which a zero power CSI-RS will be transmitted
Massive MIMO [0128] A MIMO system having a plurality of antennas can be called a massive MIMO system and stands out for being a means to improve spectral efficiency, energy efficiency and processing complexity.
[0129] Recently, the massive MIMO system was discussed in order to meet the requirements for spectral efficiency of future mobile communication systems in 3GPP. Massive MIMO is also called full-size MIMO (FD-MIMO).
[0130] LTE version-12 and subsequent wireless communication systems consider the introduction of an active antenna system (AAS).
[0131] Different from conventional passive antenna systems, in which an amplifier capable of adjusting the phase and magnitude of a signal is separated from an antenna, the AAS is configured in such a way that each antenna includes a
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26/129 active element, such as an amplifier.
[0132] AAS does not require additional cables, connectors and hardware to connect amplifiers and antennas, and therefore has high energy efficiency and low operating costs. Specifically, AAS supports electronic beam control by antenna, so it can perform the enhanced MIMO to form precise beam patterns taking into account the beam direction and beam width or 3D beam patterns.
[0133] With the introduction of improved antenna systems, such as AAS, massive MIMO having a plurality of input / output antennas and a multidimensional antenna structure is also considered. For example, when a 2D antenna array is formed instead of a linear antenna array, a 3D beam pattern can be formed using the AAS active antennas.
[0134] FIG. 7 illustrates an AAS 2D having 64 antenna elements in a wireless communication system to which the present invention is applicable.
[0135] FIG. 7 illustrates a normal 2D antenna array. A case in which Nt = Nv Nh antennas are arranged in a square shape, as shown in FIG. 10, can be considered. Here, Nh indicates the number of antenna columns in the horizontal direction and Nv indicates the number of antenna lines in the vertical direction.
[0136] When the aforementioned 2D antenna array is used, radio waves can be controlled in both the vertical (elevation) and horizontal (azimuth) directions to control the beams transmitted in 3D space. Such a wavelength control mechanism can be called a 3D beam conformation.
[0137] FIG. 8 illustrates a system in which an eNB or UE has a plurality of transmit / receive antennas capable of forming AAS-based 3D beams in a wireless communication system to which the present invention is applicable.
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27/129 [0138] FIG. 8 outlines the example described above and illustrates a 3D MIMO system using a 2D antenna array (ie, 2D-AAS).
[0139] From the point of view of the transmission antennas, the formation of a quasi-static or dynamic beam in the vertical direction, as well as in the horizontal direction of the beams, can be carried out when using a 3D beam pattern. For example, one can consider the application, such as the formation of sectors in the vertical direction.
[0140] From the point of view of the receiving antennas, an effect of increasing signal strength according to an antenna array gain can be expected when a received beam is formed using a massive receiving antenna. Therefore, in the case of the uplink, an eNB can receive signals transmitted from a UE through a plurality of antennas, and the UE can set their transmission power to a very low level taking into account the gain of the antenna. massive reception.
[0141] FIG. 9 illustrates a 2D antenna system having cross polarization in a wireless communication system to which the present invention is applicable.
[0142] The 2D planar antenna array considering the polarization can be schematic as shown in FIG. 9.
[0143] Distinguishing themselves from conventional MIMO systems using passive antennas, systems based on active antennas can dynamically control the gains of antenna elements by applying weight to an active element (eg amplifier) connected (or included in) each antenna element. Since a radiation pattern depends on an antenna arrangement, such as the number of antenna elements and antenna spacing, an antenna system can be modeled at an antenna element level.
[0144] The antenna arrangement model as illustrated in FIG. 9 can be represented by (Μ, N, P), which corresponds to parameters characterizing a
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28/129 antenna arrangement structure.
[0145] M indicates the number of antenna elements having the same polarization in each column (that is, in the vertical direction) (that is, the number of antenna elements with a + 45 ° inclination in each column or the number of elements antenna with -45 ° inclination in each column).
[0146] N indicates the number of columns in the horizontal direction (that is, the number of antenna elements in the horizontal direction).
[0147] P indicates the number of dimensions of the polarization. P = 2 in the case of cross polarization as shown in FIG. 8, while P = 1 in the case of copolarization.
[0148] An antenna port can be mapped to a physical antenna element. The antenna port can be defined by a reference signal associated with it. For example, antenna port 0 can be associated with a cell-specific reference signal (CRS) and antenna port 6 can be associated with a positioning reference signal (PRS) in the LTE system.
[0149] For example, antenna ports and physical antenna elements can be mapped from one to one. This may correspond to a case where a single cross-polarized antenna element is used for downlink MIMO or downlink transmission diversity. For example, antenna port 0 can be mapped to a single physical antenna element, whereas antenna port 1 can be mapped to another physical antenna element. In this case, two downlink transmissions are present in terms of a UE. One is associated with a reference signal for antenna port 0 and the other is associated with a reference signal for antenna port 1.
[0150] Alternatively, a single antenna port can be mapped to multiple physical antenna elements. This may correspond to a case where a single antenna port is used for beam forming. The conformation of
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29/129 beam can cause the downlink transmission to be directed to a specific UE using multiple physical antenna elements. This can be accomplished using an antenna array composed of multiple columns of multiple cross-polarized antenna elements in general. In this case, a single downlink transmission derived from a single antenna port is present in terms of a UE. One is associated with a CRS for antenna port 0 and the other is associated with a CRS for antenna port 1.
[0151] That is, an antenna port represents the downlink transmission in terms of a UE instead of the substantial downlink transmission from a physical antenna element in an eNB.
[0152] Alternatively, a plurality of antenna ports can be used for downlink transmission and each antenna port can be multiple physical antenna ports. This may correspond to a case where the antenna array is used for downlink MIMO or downlink diversity. For example, antenna port 0 can be mapped to multiple physical antenna ports and antenna port 1 can be mapped to multiple physical antenna ports. In this case, two downlink transmissions are present in terms of a UE. One is associated with a reference signal for antenna port 0 and the other is associated with a reference signal for antenna port 1.
[0153] In FD-MIMO, MIMO pre-coding of a data stream may be subject to antenna port virtualization, transceiver unit virtualization (TXRU) and an antenna element pattern.
[0154] In antenna port virtualization, a stream in an antenna port is pre-coded in the TXRU. In TXRU virtualization, a TXRU signal is pre-coded into an antenna element. In the antenna element pattern, a signal radiated from an antenna element can have a directional gain pattern.
[0155] In conventional transceiver modeling, it is assumed that
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30/129 static one-to-one mapping between an antenna port and the TXRU and the TXRII virtualization effect is integrated into an antenna pattern (TXRII) including the effects of both the TXRII virtualization and the antenna element pattern.
[0156] Antenna port virtualization can be performed using a frequency selective method. In LTE, an antenna port is defined together with a reference (or pilot) signal. For example, for transmitting pre-coded data on an antenna port, a DMRS is transmitted in the same bandwidth as for a data signal, and both DMRS and the data signal are pre-coded through the same pre-coded data. encoder (or the same virtualization pre-encoding as TXRII). For CSI measurement, a CSI-RS is transmitted through multiple antenna ports. In CSI-RS transmission, a precoder that characterizes the mapping between a CSI-RS and TXRII port can be designed as an automatrix so that a UE can estimate a virtualization precoding matrix from TXRII to a pre vector - data encoding.
[0157] TXRII 1D virtualization and TXRII 2D virtualization are discussed as TXRII virtualization methods, which will be described below with reference to the drawings.
[0158] FIG. 10 illustrates models of transceiver unit in a wireless communication system to which the present invention is applicable.
[0159] In the virtualization of TXRII 1D, M_TXRU TXRUs are associated with M antenna elements in a single single column antenna array having the same polarization.
[0160] In 2D TXRII virtualization, a TXRII model corresponding to the antenna array model (Μ, N, P) of FIG. 8 can be represented by (M_TXRU, N, P). Here, M_TXRU denotes the number of 2D TXRUs present in the same column and in the same polarization, and M_TXRU <Μ all the time. That is, a total number of TXRUs is M_TXRU * Nx P.
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31/129 [0161] TXRII virtualization models can be divided into TXRII virtualization model option 1: subarray partition model as illustrated in FIG. 10 (a), and TXRII virtualization model option 2: full connection model as illustrated in FIG. 10 (b) according to the correlation between the antenna elements and the TXRII.
[0162] Referring to FIG. 10 (a), the antenna elements are partitioned into multiple groups of antenna elements and each TXRII is connected to one of the groups in the case of the subarray partition model.
[0163] Referring to FIG. 10 (b), multiple TXRII signals are combined and distributed to a single antenna element (or array of antenna elements) in the case of the complete connection model.
[0164] In FIG. 10, q is a transmission signal vector of M co-polarized antenna elements in a single column, w is a broadband TXRII virtualization weight vector, W is a broadband TXRII virtualization weight matrix , ex is a signal vector of M_TXRU TXRUs.
[0165] Here, the mapping between the antenna ports and the TXRUs can be 1 to 1 or 1 to many mapping.
[0166] FIG. 10 shows an example of mapping TXRU elements to antenna and the present invention is not limited to it. The present invention can also be applied to the mapping between TXRUs and antenna elements performed in different ways in terms of hardware.
Channel Status Information (CSI) - Reference Signal Definition (CSI-RS) [0167] With respect to a server cell and UE that are configured with transmission mode 9, the UE can be configured with a configuration of CSI-RS resource. With respect to a server cell and UE that are configured with transmission mode 10, the UE can be configured with a
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32/129 or more CSI-RS resource configurations. The following parameters that the UE assumes non-zero transmission power for a CSI-RS are configured through upper layer signaling for each CSI-RS resource configuration:
[0168] - CSI-RS resource configuration identity (when a UE is configured with transmission mode 10) [0169] - The number of CSI-RS ports [0170] - CSI-RS configuration [0171] - CSI RS subframe configuration (Icsi-rs) [0172] - UE assumption for a reference PDSCH transmission power P _c for CSI return (when a UE is configured with transmission mode 9) [0173] - Assumption of the UE for a transmission power of reference PDSCH P _c for return of CSI for each CSI process, when a UE is configured with the transmission mode 10. In the case where the CSI subframe defines Ccsi.o and Ccsi.- i, they are configured by the upper layer signaling for a single CSI process, Pc is configured for each of the CSI subframe sets of the corresponding CSI process.
[0174] - Pseudo-random sequence generator parameter (mo) [0175] - CDM type parameter, when a UE is configured with the upper layer parameter CSI-Reporting-Type and the CSI-Reporting-Type is defined as “CLASS A” for the CSI process.
[0176] - The top layer parameter qcl-CRS-lnfo-r11, when a UE is configured with transmission mode 10, the assumption of the UE regarding the QCL type B of the CRS antenna port which has the following parameters and ports of CSI-RS antenna:
[0177] - qcl-Scramblingldentity-r11.
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33/129 [0178] - crs-PortsCount-r11.
[0179] - mbsfn-SubframeConfigList-rl 1.
[0180] P _c is an assumed ratio of PDSCH EPRE to CSI-RS EPRE when a UE derives the CSI return and obtains a value in a range of [-8, 15] dB with a step size of 1 dB. Here, the PDSCH EPRE corresponds to the symbol number for a ratio of the PDSCH EPRE to the cell-specific RS EPRE.
[0181] A UE does not expect the CSI-RS and PMCH to be configured in the same subframe as a server cell.
[0182] With respect to the type 2 frame structure serving cell and the 4 CRS ports, a UE does not expect to receive the CSI-RS configuration index that belongs to the set [20-31] for a normal or to the set [16-27] for an extended PC case.
[0183] A UE can assume that the CSI-RS antenna port of the CSI-RS resource configuration is in the QCL for delay spread, Doppler spread, Doppler shift, average gain and average delay.
[0184] A UE configured with transmission mode 10 and type QCL B can assume that the antenna ports 0 to 3 associated with the qcl-CRS-lnfo-r11 corresponding to the CSI-RS resource configuration and the antenna ports 15 to 22 corresponding to the CSI-RS resource configuration are in the QCL for Doppler shift and Doppler scattering.
[0185] A UE configured with transmission 10 and upper layer parameter CSI-Reporting-Type, CSI-Reporting-Type is defined as “class B”, in which the number of CSI resources configured for the CSI process is one or more, and QCL type B is defined, the UE does not expect to receive resource configuration from CSI-RS for a CSI process that has value of the upper layer parameter qcl-CRS-lnfo-r11.
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34/129 [0186] In a subframe constructed / configured for a CSIRS transmission, the reference signal sequence ^ 7, „ _s (w) can be mapped to a complex value modulation (//) symbol at _kl q _U e are used as reference symbols for the antenna port p. Such mapping depends on the top layer parameter CDMType.
[0187] In the case where CDMType does not correspond to CDM4, a mapping can be performed according to Equation 12 below.
[Equation 12] ^a k ^ = f- 0 for X and {15,16} normal cyclic black for Χε [17,18} prefixocyclic · πormal [-1 for // and {19.20} normal cyclic black | - 7 for X = {21,22} nwmal cyclic prefix [-0 for pe [15, lõç normal cyclic prefix | -3 for X and {17,18} normal cyclic prefix
I - â for X and [19..20}. normal cyclic prsfcs [-9 for X and {2L22.} normal cyclic black p reference signal settings CS1 0-19, normal cyclic prefix / = / M 2 / ”reference signal configurations CSÍ 20 - 31, normal cyclic prefix
I / CS1 reference signal settings 0 - 27, extended cyclic prefix [1 X ε {15,17,19,21} ”} (- if X s {10,18,20,22}
Γ = 0.1 í F = 0.1 ..., 7¾¾ -1 [0188] In the case where CDMType corresponds to CDM 4, a mapping can be performed according to Equation 13 below.
[Equation 13] = ^W p '( ^Í ) - ^r l, nS ^m ^
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12/35
1 = 1 + 12 ^ - (1 + 6 paraj / e {17, .18,21,22), ddton & rmal black, A ^ _g = 8 './ . ^Λ : · ί <
I 6.1 pars pe (15, .16, .1718 (,. black del iso normal A ^ _s = 4 _f ., · 'CSi referral signal settings 0 -19, prefix normal medical
Í = / f ’>
; 2Γ 'CSi reference signal configurations 20 - 3 1, black delice normal r = o, i = 0.1 = 21 '+ Γ' m '= [0189] w _p ' (i) in Equation 13 is determined by Table 6 below. Table 3 represents the sequence w _p . (I) for CDM 4.
[Table 3] ________________________________________________
15 15.17 [1111] 16 16.18 [1 -1 1 -1] 17 19.21 [1 1 -1 -1] 18 20.22 [1 -1 -1 1]
Numeroloqia OFDM [0190] As more communication devices require greater communication capacity, the need for mobile broadband communication that improves over the existing radio access technology (RAT) has grown. In addition, the massive MTC (Machine-Type Communications) offering multiple services anytime and anywhere by connecting a plurality of devices and objects is also one of the important issues considered in next generation communication. In addition, a concept of a communication system has been discussed in which a service and / or a UE is
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36/129 sensitive to reliability and latency. As such, the introduction of a next generation RAT has been discussed today, which considers improved mobile broadband communication, massive MTC, Ultra-Reliable and Low Latency Communication (URLLC), among others, and such technology is generally called “new RAT (NR)”.
[0191] The new RAT system uses the OFDM transmission scheme or the similar transmission scheme, representative of the OFDM numerology represented in Table 4 below.
[Table 4]
Parameter value Spacing between subcarriers (*) 60kHz OFDM symbol duration 16.33x / s Cyclic prefix duration (CP) 1.30 / zs / 1.17 // SS System bandwidth 80MHz N ² of available subcarriers 1200 Subframe duration 0.25ms N ² of OFDM symbols per subframe 14 symbols
Autonomous subframe structure [0192] In the TDD system, in order to minimize data transmission delay, the autonomous subframe structure for which a control channel and a data channel are subject to TDM as illustrated in FIG. 11 was considered in the new 5 ² Generation RAT.
[0193] FIG. 11 illustrates an autonomous subframe structure to which the present invention can be applied.
[0194] The shaded area in FIG. 11 shows a transport region of a physical channel PDCCH to forward the DCI, and the dark area shows a transport region of a physical channel PUCCH to forward the Uplink Control Information (UCI).
[0195] The control information that an eNB forwards to an UE through
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37/129 of the DCI includes information on a cell configuration that the UE needs to know, specific DL information, such as DL programming, among others, and / or UL specific information, such as UL grant. In addition, the control information that an eNB forwards to a UE through the UCI includes HARQ ACK / NACK reporting for UL data, CSI reporting for DL channel status and / or Programming Request (SR), and so on.
[0196] The area not marked in FIG. 11 can be used for the transport region of a physical channel PDSCH for downlink data (DL) and a transport region of a physical channel PUSCH for uplink data (UL). In the characteristics of such a structure, a DL transmission and an UL transmission can be progressed sequentially in a subframe (SF), a DL data can be transmitted, and an UL ACK / NACK can be received in the corresponding SF. Consequently, according to this structure, the time required to retransmit the data is reduced when a data transmission error occurs, and thanks to this, the delay until the final data forwarding can be minimized.
[0197] In such an autonomous subframe structure, a time interval is necessary for a process in which an eNB and UE exchange from a transmission mode to a reception mode or a process in which an eNB and UE exchange from one reception mode to a transmission mode. For this purpose, a part of the OFDM symbols in the timing switch from DL to UL can be configured as GP, and this type of subframe can be called “standalone SF”.
Analog Beam Conformation [0198] In the Millimeter Wave range (mmW), a wavelength becomes short and an installation of a plurality of antenna elements is available in the same area. That is, the wavelength in the 30 GHz band is 1 cm, and therefore an installation in total of 64 (8X8) antenna elements
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38/129 is available in a two-dimensional array format with intervals of 0.5 lamda (wavelength) on the 5 by 5 cm panel. Therefore, in the mmW range, the beamform gain (BG) is increased using a plurality of antenna elements, and consequently, the coverage is increased or the data transfer speed becomes greater.
[0199] In this case, each antenna element has a Transceiver Unit (TXRU) so that it is available to adjust a transmission power and phase, and the independent beam conformation is available for each frequency resource. However, it has a problem that effectiveness is deteriorated in a cost aspect when TXRUs are installed on all of the approximately 100 antenna elements. Consequently, it was considered a method to map a plurality of antenna elements in a single TXRU and to adjust a beam direction by an analog phase shifter. Such an analog beam forming technique can assume only one beam direction across the entire range, and there is a disadvantage that frequency-selective beam forming is unavailable.
[0200] As an intermediate form between m BF Digital and an analog BF, the number B of the hybrid BF can be considered, which is less than the number Q of the antenna element. In this case, the directions of the beams that can be transmitted simultaneously are limited less than the number B; even this is changed according to a connection scheme between number B of TXRUs and number Q of antenna elements.
[0201] Furthermore, in the case where multiple antennas are used in the New RAT system, a hybrid beam forming technique has emerged in which the digital beam forming and the analog beam forming are combined. In this case, the analog beam conformation (or radio frequency (RF) beam conformation) means an operation to perform pre-coding (or
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39/129 combination) in an RF terminal. In the hybrid beam forming technique, each of a baseband terminal and an RF terminal performs pre-coding (or combination), and thanks to this, there is the advantage that an approximate performance of the digital beam forming can be obtained while the number of RF chains and the number of digital (D) / analog (A) (or A / D) converters is reduced. For convenience of description, a hybrid beam forming structure can be represented by N transceiver units (TXRUs) and M physical antennas. Then, the digital beam conformation for L layers of data that will be transmitted in a transmitter can be represented by N by the matrix L. Next, the analog beam conformation is applied in which the transformed N digital signals are transformed into analog signals through a TXRII, and then represented by an M matrix by N.
[0202] FIG. 12 is a diagram schematically illustrating a hybrid beam forming structure in the aspect of a TXRII and a physical antenna. FIG. 12 exemplifies the case where the number of digital beams is L and the number of analog beams is N.
[0203] In the new RAT system, an orientation was considered: it is designed so that an eNB can change the analog beam conformation in a symbol unit, and the most efficient beam conformation is supported for an UE located in an area specific. In addition, when N TXRUs and M RF antennas illustrated in FIG. 12 are defined as a single antenna panel, in the Nova RAT system, the way to introduce a plurality of antenna panels was also considered, to which the independent hybrid beam conformation can be applied.
[0204] In the case where an eNB uses a plurality of analog beams, an analog benefit beam to receive a signal can be changed according to each UE. Therefore, it was considered a beam scan operation
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40/129 that, for at least the synchronization signal, system information, paging, among others, a plurality of analog beams that an eNB will apply to a specific Subframe (SF) is changed for each symbol so that all UEs have reception changes.
[0205] FIG. 13 is a diagram schematically illustrating a synchronization signal in the DL transmission process and a beam scan operation for system information.
[0206] The physical resource (or physical channel) in which the Nova RAT system system information is transmitted in FIG. 13 is called the physical diffusion channel x (xPBCH).
[0207] Referring to FIG. 13, the analog beams belonging to different antenna panels in a single symbol can be transmitted simultaneously. In order to measure a channel for each analog beam, as shown in FIG. 13, an introduction of a beam RS (BRS) was discussed in which a beam RS (BRS) is introduced, which is an RS to which a single analog beam (corresponding to a specific antenna panel) is applied and transmitted . The BRS can be defined for a plurality of antenna ports, and each BRS antenna port can correspond to a single analog beam. At this time, unlike BRS, a sync signal or xPBCH can be transmitted and all analog beams in a group of analog beams can be applied in order to be received well by an arbitrary UE.
LTE RRM measurement [0208] The LTE system supports an RRM operation for power control, programming, cell search, cell search, handover (transfer between cells), radio link monitoring or connection, establishment and restoration of connection, and so on. A server cell can request RRM measurement information, which is a measurement value
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41/129 to perform an RRM operation for a UE. Representatively, in the LTE system, a UE can measure / obtain information such as power received from the reference signal (RSRP), quality received from the reference signal (RSRQ), among others, and report them. Specifically, in the LTE system, a UE receives “measConfig” as an upper layer signal for an RRM measurement from a server cell. The UE can measure RSRP or RSRQ according to the “measConfig” information. Here, the definition of RSRP, RSRQ and RSSI according to TS 36.214 of the LTE system is as follows.
[RSRP] [0209] The power received from the reference signal (RSRP) is defined as the linear average over the power contributions (in [W]) of the resource elements that carry cell-specific RSs (CRS) within the measurement frequency bandwidth considered. To determine the RSRP, the CSR RO according to TS 36.211 [3] must be used. In case the UE can reliably detect that R1 is available, it can use R1 in addition to RO to determine RSRP.
[0210] The reference point for the RSRP should be the antenna connector of the UE.
[0211] In case the receiver diversity is in use by the UE, the reported value should not be less than the corresponding RSRP of any of the individual diversity branches.
[RSRQ] [0212] The Quality Received from the Reference Signal (RSRQ) is defined as the ratio NxRSRP / (RSSI of E-UTRA bearer) (that is, RSSI of E-UTRA bearer vs NxRSRP), where N is the number of RB's of the E-UTRA carrier RSSI measurement bandwidth. Measurements on the numerator and denominator should be made over the same set of resource blocks.
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42/129 [0213] The EIITRA Carrier Signal Intensity Indicator (RSSI) comprises the linear average of the total received power (in [W]) observed only in OFDM symbols containing reference symbols for antenna port 0, at measurement bandwidth, by the N number of resource blocks by the UE from all sources (including co-channel server and non-server cells), channel interference, thermal noise, among others. In the event that the upper layer signaling indicates certain subframes for making RSRQ measurements, RSSI can be measured across all OFDM symbols in the indicated subframes.
[0214] The reference point for the RSRQ should be the antenna connector of the UE.
[0215] In case the receiver diversity is in use by the UE, the reported value should not be less than the corresponding RSRQ of any of the individual diversity branches.
[0216] The RSSI can correspond to the received broadband power including the thermal noise and the noise generated at a receiver within the bandwidth defined by the receiver's pulse forming filter.
[0217] The reference point for the measurement should be the antenna connector of the UE.
[0218] In case the receiver diversity is in use by the UE, the reported value should not be less than the corresponding UTRA carrier RSSI of any of the individual antenna branches received.
[0219] According to the definition, a UE operating in the LTE system may be allowed to measure the RSRP in a bandwidth corresponding to one of 6, 15, 25, 50, 75 and 100 RBs (resource blocks), through the information element (IE) in relation to a measurement bandwidth transmitted in the type 3 system information block (SIB3) in the case of an Intra-frequency measurement, and
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43/129 through an allowable measurement bandwidth transmitted in a type 5 system information block (SIB5) in the case of an inter-frequency measurement. Alternatively, in the event that IE does not exist, the UE can measure in a frequency band the entire DL system by default. At this time, in the case where the UE receives the allowable measurement bandwidth, the UE can regard the corresponding value as the maximum measurement bandwidth and can measure the RSRP value freely within the corresponding bandwidth / value. However, in order for a server cell to transmit the UE defined as broadband RSRQ (WB) and set the allowable measurement bandwidth to be 50 RBs or more, the UE must calculate the RSRP value for the entire width of permissible measuring band. Meanwhile, RSSI can be measured in the frequency band that a UE receiver has according to the definition of the RSSI bandwidth.
[0220] FIG. 14 illustrates an array of panel antennas to which the present invention can be applied.
[0221] Referring to FIG. 14, a panel antenna array includes the number Mg of panels in a horizontal domain and the number Ng of panels in a vertical domain, and a panel can include M columns and N rows. Particularly, in this drawing, a panel is illustrated based on the cross-polarized antenna (X-in). Therefore, the total number of antenna elements can be 2 * M * N * Mg * Ng.
New Code Dictionary Proposal [0222] From now on, a new code dictionary scheme for UL pro-coding is proposed in an environment such as the New RAT. In addition, it is also proposed to restrict the subset of the UL code dictionary.
[0223] As illustrated in Fig. 14, a multi-panel function is supported in
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New RAT, but, but in the present disclosure, a code dictionary scheme is proposed taking into account a single panel preferably for the convenience of the description.
[0224] The Discrete 2D Fourier Transform beam can be defined as Equation 14, which can be applied to the array of 2D antennas on a single panel.
[Equation 14]
V „, = 1 exp (7 '[0225] Here, m1 and m2 correspond to the code dictionary indexes 1 - DFT of the first and second domains, respectively, in addition, N1 and N2 correspond to the number of antenna ports for each polarization of the first dimension and the second dimension in a panel, respectively, and o1 and o2 correspond to oversampling factors of the first dimension and the second dimension in a panel, respectively.
[0226] The code dictionary proposed as in Equation 14 follows the double stage structure as represented in Equation 15.
[0227] [Equation 15]
W = W-iWj [0228] Here, W1 (a first PMI) represents the long-term / broadband property, and performs the function of beam grouping and / or broadband power control for each beam mainly. W2 (a second PMI) represents the short-term / subband property, and plays the role of
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45/129 beam selection in a beam group selected by W1 and co-phasing for each antenna port polarization having cross polarization.
[0229] Table 5 exemplifies the LTE UL code dictionary for transmission on the antenna ports {20, 21}.
[Table 5]
code dictionary index Number of layers illllii;; 2 0 i p77 J Ί 1 | T o i 41 | _o 1J 1 1 ΓV2 Ί - 2 1 Γ4i L Π J - 3 1V2 Ίj - 4 V2 _ ( L] - 5 1 Γ ) Ί1J -
[0230] Table 6 exemplifies the LTE UL code dictionary for transmission on the antenna ports {40, 41.42, 43} with t »= l.
[Table 6]
code dictionary index Number of layers 0-7 1 1 1 1 1 1 1 11 1 1 1 1 1 1 1 1 j 1 j 1 j 1 j2 1 2 i 2 -1 2 ~ j 2 1 2 j 2 -1 2 ~ j j 1 - ί j 1 - ί8-15 1 1 1 1 1 1 1 11 -1 1 -1 1 -1 1 -1 1 -j 1 -j 1 -j 1 -j2 1 2 ] 2 -1 2 ~ j 2 1 2 j 2 -1 2 ~ jL ¹ - ί -1 j - ί -1 j L ¹ 16-23 1 1 1 1 0 0 0 01 0 1 0 1 0 1 0 1 1 1 1 1 1 1 12 1 2 -1 2 j 2 ~ j 2 0 2 0 2 0 2 0 0 0 0 1 -1 j L-
[0231] Table 7 exemplifies the LTE UL code dictionary for transmission on the antenna ports {40, 41.42, 43} with u = 2.
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46/129 [Table 7]
code dictionary index Number of layers u = 20-31 0 '1 0 ’ 1 0 1 0 1 1 01 1 01 -i 01 -j 0 2 0 12 0 12 0 12 0 1 0 -i _ ° Á 0 1 0 -14-71 0  1 0 ’ '1 0 ’ T o ’ 1 -1 01 -1 01 j 01 j 0 2 0 12 0 12 0 12 0 1 0 -i .0 Á 0 1 0 -18-11"1 0" 1 0 ’ ’1 0’ ’1 0 1 0 11 0 11 0 11 0 1 2 1 02 1 02 -1 02 -1 0 0 1 0 -1 0 1 0 -112-15"1 0" 1 0 ’ "1 0" ’1 0 1 0 11 0 11 0 11 0 1 2 0 12 0 -12 0 12 0 -1 1 0 1 0 -1 0 -1 0 > - -- -> - -- -
[0232] Table 8 exemplifies the LTE UL code dictionary for transmission on the antenna ports {40, 41.42, 43} with υ = 3.
[Table 8]
code dictionary index Number of layers 0-3 2 T o o ’1 0 00 1 00 0 12 ’1 0 0’-10 00 1 00 0 12 T o o ’0 1 01 0 00 0 12  1 0 0 '0 1 0-10 00 0 14-7 2 T o o '0 1 00 0 11 0 02  1 0 0 '0 1 00 0 1-10 02 '0 1 0'1 0 01 0 00 0 12  0 10 '1 0 0-10 00 0 18-11 2 '0 1 0'1 0 00 0 11 0 02  0 10 '1 0 00 0 1-10 02 '0 1 0'0 0 11 0 01 0 02  0 10 '0 0 11 0 0-10 0
[0233] Table 9 exemplifies the LTE UL code dictionary for transmission on the antenna ports {40, 41.42, 43} with υ = 4.
[Table 9]
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code dictionary index Number of layers ^{υ =} ^ 0 2 1 0 0 0 ’0 10 00 0 100 0 0 1
[0234] The NR can support that an UE can report the capacity for a maximum number of space layer (N) for UL transmission.
[0235] In addition, NR supports the UL code dictionary for a UE based on reported performance, and at least one of the following can be supported.
[0236] - Alt1: A network configures multiple code dictionaries corresponding to the number of antenna ports, respectively.
[0237] - Alt2: A network configures a scalable / nested code dictionary that supports a variable number of antenna ports.
[0238] - Alt3: A network configures a dictionary of codes that is the same as a capacity of the UE.
[0239] - Alt4. A UE recommends a subset of code dictionaries. This Alt can be included in at least one of the Alts described above.
[0240] A code dictionary corresponding to TX antenna ports of a given number can be fixed to a specific or configurable code dictionary.
[0241] As a UL code dictionary structure, at least one of two types can be supported.
[0242] - Alt 0: A single state code dictionary [0243] - Alt 1: A double state code dictionary [0244] When a UL code dictionary is designed, the reuse of the LTE code dictionary, the influence on multiple panels, among other factors, should be considered.
[0245] In NR, as a waveform for UL, both Multiplexing by
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Division in Orthogonal Frequencies with Cyclic Prefix (CP-OFDM) regarding DFTsOFDM can be used. Since a waveform such as DFTs-OFDM is considered in LTE, its main design objective is to reduce the peak to medium power ratio (PAPR) considering the property of a single carrier. As a result, at LTE, a code dictionary with the property of cubic metric preservation is used. Such a code dictionary has a property in which the sum of the layer power for each port is set to be the same for grade> 1 and a code word (for example, noncoherent / partial) is included, which you can turn off (or do not select / do not activate) a specific antenna port (an antenna element in some cases, but hereinafter, simply called “port” for the convenience of the description) for grade = 1.
[0246] The present invention proposes a UL code dictionary construction / configuration / application scheme that can be applied to a new wireless communication system.
[0247] Before describing this, referring to FIG. 15, a schematic UL data transmission process is described between a UE and a gNB.
[0248] FIG. 15 illustrates a schematic UL data transmission process between a UE and a gNB that can be applied to the present invention.
[0249] 1) A UE performs a report (of performance) for the transmission / code dictionary configuration of the Drill Reference Signal (SRS) of the UE. At this point, the information that the UE is able to report on may include the (maximum) number of antenna ports on a panel (or group of ports), the number of panels (or group of ports, hereinafter referred to simply as “Panel”), the calculation power of Rx (for example, whether it is capable of calculating a complex code dictionary, such as the type II DL code dictionary, or whether it will support non-linear pre-coding, etc. ), the number of recommended EU ports for
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49/129 SRS transmission and / or code dictionary, waveform information (for example, information as to whether it is CP-OFDM or DFTs-OFDM) and / or whether it will transmit multiple panels, among others.
[0250] 2) The gNB can indicate configuration information for the SRS resource (s) to the UE using Radio Resource Control (RRC), DCI and / or MAC CE, and so on, using the information reported by the UE. In this case, the configuration information for the SRS resource (s) may include the number (N) of SRS resources, the number of transport ports (x_i) (i = 0, N-1) of the i- is very
SRS and / or analog beam conformation information for each SRS resource, among others.
[0251] 3) The U transmits an SRS to the gNB using the SRS configuration information received from the gNB.
[0252] 4) The gNB can perform channel measurement and / or CSI calculation (SRS Resource Indicator (SRS), CQI, RI, Transmitted Pre-Coding Matrix Indicator (TPMI, etc.) using the transmitted SRS from the UE, and inform the information, MCS and / or UL power information, among others, to the UE through the UL concession, among others. At this moment, even in the case where the gNB receives the SRS through the port X, gNB can report MCS and TMPI / RI information, and so on, which is calculated using the Y port TMPI / RI.
[0253] 5) The UE can perform the transmission of UL data using the information received.
[0254] In the case where the UE is provided with multiple panels (or group of antenna ports, hereinafter simply called “panel, the factors that should be considered for a code dictionary scheme are as follows:
[0255] - The number of panels supported in the UL code dictionary
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50/129 [0256] - The number of ports supported for each panel [0257] - If the UE is able to have a different number of ports for each panel [0258] In the case that a code dictionary is designed taking into account all parameters, a code dictionary scheme can become very difficult. Therefore, the present invention proposes a code dictionary scheme assuming a single panel (defined as a group of doors in which the peak-to-average power ratio (SINR) is similar, hereinafter referred to simply as "panel" ). Each panel can be linked / linked to an SRS resource, and the number of antenna ports on each panel can be linked / linked to the number of SRS ports on each SRS resource.
[0259] Therefore, a panel selection can be performed by a single SRI indication received from gNB. In this case, the PMI / RI / MCS corresponding to the number of SRS ports of the indicated SRI can be indicated for the UE. In the event that a plurality of code dictionaries (candidates) is indicated in the UL, gNB can also indicate the code dictionary configuration for the UE. In addition, or alternatively, in the event that the appropriate CP-OFDM code dictionary, which is a standard waveform, and the appropriate DFTs-OFDM code dictionary are designed differently, the UE may indicate the waveform to be used and the code dictionary corresponding to the waveform for the UE additionally, considering the measured channel interference, among others. In addition, or alternatively, using the indicated MCS information (SINR or CQI), the UE (for example / that is, a UE whose geometry is unsatisfactory) of which the MCS (SINR or CQI) is a specific threshold or lower, can operate based on DFTs-OFDM, and can use the appropriate code dictionary.
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51/129 [0260] Hereinafter, the case where gNB indicates M (M> 1) SR resources for the UE is described. In this case, the gNB can explicitly indicate a plurality of SRIs to the UE with a scheme, such as a bitmap, or it can indicate using pairing / grouping of M (resources) of SRS selected from N (resources) of SRS configured implicitly for the HUH.
[0261] For example, the case where the number of SRS resources indicated is 2 (M = 2) is described. At this time, it is assumed that each resource is provided with Xi (i = 0, 1) SRS ports, respectively, as described below.
[0262] - SRS resource configured O (port Xo) for Panel 0, [0263] - SRS resource configured 1 (port Xi) for Panel 1, [0264] At this time, the UE can recommend the port number , among others, represented by Xo, Xi to gNB (for example, when reporting performance). In the event that two SRS features are configured / applied to the UE, the UE can identify which two panels are used, and calculate the final PMI by configuring the multi-panel code dictionary. In the case where the port numbers of Xo and Xi are the same, the final code dictionary I ' ^s Vj and (ϊ = <M) .v = 1 can be configured using PMI (ie I ¥ _t i is, v ₀ , Vj for grade 1) indicated for each resource in the same code dictionary.
[0265] For the case of the UE panel configuration, in order to transmit / receive a signal in all directions, the configuration (for example, in the case of two UD antenna panels) of opposite oriented directions can be considered . In this case, since a direction towards gNB, the angle of deviation (AoD), Angle of Arrival (AoA), zenith of the angle of deviation (ZoD) and / or latency can be changed, a panel correction is also additionally takes necessary. Such a panel correction term can be represented as / = aexptjú). Here, a (e.g., a & {l, y / ÕÃ, ^ 0.25,0}) can represent an amplitude and ^ (e.g. ^ QPSKor8PSK) can represent a phase, and gNB can indicate
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52/129 the information to the UE additionally. At this time, the convenience of signaling, for example, the GNB may indicate that the 0 order configured SRS action can be assumed to be a reference resource, and only the phase and / or amplitude information γ = aexptjú) to the first configured order of the SRS resource for the UE. In this case, the final code dictionary can be configured as ^v o [0266] For grade 2, the final code dictionary can be configured as
Alternatively, the final code dictionary is configured as ^v o ^v o / ^V i - / V!
<U), and in this case, it is preferable that y® is orthogonal to each other for each layer. The code dictionary is represented as a code dictionary in which normalization is not performed, and in the case where 1 column normalization is performed, ₂ can be multiplied for the code dictionary. For example, grade 2 of the LTE DL code dictionary can be applied.
[0267] The scheme is a structure that consists of using the same co-phase for each layer / each panel, and therefore, performance degradation is anticipated. Therefore, the present invention proposes to configure the channel correction term ^r · 6 = ⁰ ^) independently for each layer in order to support grade 2. ¹ includes phase and / or amplitude information. The channel correction term should only be applied to one WB, and the payload can be reduced to the maximum. Alternatively, the channel correction term should be applied to an SB, and performance can be maximized. Alternatively, the phase and amplitude components can be applied by being separated by WB / SB (or SB / WB). Alternatively, the bit numbers corresponding to WB and SB are allocated / configured differently (for example, WB = 2 bits, SB = 1 bit), the
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53/129 payload size and performance can be balanced.
[Equation 16]
Á GO '· laughs-V I -. Γ ™ T ·. · »Z
I | onáe V. ^ = I | eC =
LMr j [0268] In the case of the scheme according to Equation 16, there is a problem that the panel correction term is increased as the layer increases. In order to solve it, a transmission is performed based on the CoMP operation, such as coherent and / or non-coherent (JT) joint transmission, and the like, the scheme of restricting a degree of transmission to 2 can be proposed. Alternatively, in the case of a code dictionary used in a transmission based on the CoMP operation, such as JT coherent and / or non-coherent, similar to “Config. 1 of the LTE DL Class A code dictionary ”a code dictionary scheme may be limited to configuring grade 2 only with a combination of identical beams. In this case, regardless of grade 1 and grade 2, a panel correction term, Y = ^aQX PÍj &), can be used.
[0269] The Grade 1 and Grade 2 structures of Code Dictionary Config 1 are as represented in Equation 17 below.
[Equation 17] j V (J Vç V.-. [
Degree! i ~ L Grade2: i
J 1 $ Λ I [0270] In the event that a code dictionary structure used on a single panel is configured with the dual stage code dictionary (W = W1W2) for frequency selective pre-coding, a correction term r ^{= a and x} P (Í &) for a panel can be transmitted together with W1. In addition or alternatively, in the case where frequency selectivity is high for each SB, Z = «exp (j0) _can be transmitted together with W2. In addition or alternatively, for an efficient TMPI indication, an amplitude can be indicated by W1 (WB or partial band unit (PB)), and a phase can be indicated by W2 (unit
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54/129 of SB).
[0271] The scheme described above can also be applied to periodic and semi-permanent transmission as well as aperiodic transmission (based on UL concession). In addition, the proposed scheme is mainly described with the UL code dictionary, but it is apparent that the scheme can also be configured / applied in an identical / similar way to the multi-panel DL code dictionary.
[0272] In the event that a gNB indicates the SRI, MCS and / or TMPI + RI with a UL grant, the following options can be considered.
[0273] 1. DCI payload varies according to paragraph ² SRS resources: As an example of the two SRSs are configured as described above, one may consider the following.
[0274] 1-A: (SRI = 0) + (TPMIO) + (SRI = 1) + (TPMI1) + MCS (for example, based on CQI) + IR: In the case of the method, the CQI is calculated considering if a single aggregated TPMI (TPMI0 + TPMI1) considering multiple panels (in this case, the proposed panel correction PMI can be additionally considered), and based on this, the MCS can be calculated. As a representative use case, the non-coherent JT can be considered (or the coherent JT, in case the panel correction PMI is additionally considered).
[0275] 1-B. (SRI = 0) + (SRI = 1) + TPMI + MCS (for example, based on CQI) + IR: In the case of the method, the CQI is calculated by selecting / applying the TPMI in the code dictionary that corresponds to a single aggregated SRS port number considering multiple panels (a plurality of door groups), and based on this, the MCS can be calculated. As a representative use case, JT can be considered coherent.
[0276] 1-C. (SRI = 0 + TPMI0 + RI0 + MCS0 (corresponding to SINR0)) + (SRI = 1 + TPMI1 + RI1 + MCS1 (corresponding to SINR1)): In the case of the method, the MCS
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55/129 can be calculated for each resource. For this, the gNB indicates the MCSO calculated for the UE using the TPMIO corresponding to a reference SRS resource, and MCS1 can be indicated to the UE using the differential MCS that represents a difference between the SINR and SINRO when the aggregated TPMI is used . At this time, IR can also be configured / indicated by the IR reference and differential IR similar to the MCS, and only a complete IR can be configured / indicated as in case 1-A.
[0277] 2. Common DCI size: In the case of the method, the DCI size for indicating SRI, MCS and / or TPMI / RI can be set to a maximum value, for example, it can be configured / indicated as the format such as (joint coding two SRI indications) + (joint coding of two TMPI indications) + MCS + RI + additional TPMI (for example (F ^{= to exp} ^).
[0278] In the event that a plurality of SRIs are used as described in the method, the SRI field can be configured as represented in Table 10, for example. Table 10 represents an example of configuration of the 2-bit SRI field, and it is assumed that (SRS resources 1, 2, 3 and 4) exist as the configurable SRS resource.
[Table 10] __________________________________________
state number of SRS resources 00 1 01 1.2 10 1.3 11 1,2,3,4
[0279] In Table 10, the use of the 2-bit SRI is assumed, here, the state “00” corresponds to the most preferred SRS resource or to a single selection corresponding to the most preferred panel, the state “01” or “ 10 ”corresponds to a subset of the entire SRS resource set in which two preferred SRS resources are transmitted cooperatively, such as by non-coherent / coherent JT, and the like, and status“ 11 ”corresponds to the SRS resource
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56/129 integer in which the entire configured SRS resource is transmitted cooperatively, such as non-coherent / coherent JT, and the like.
[0280] In the case where each state is used only for the use of a specific resource selection, each state can be configured / applied with only a single value of the configured / selected resource, as shown in Table 11.
fTable 11]state Number of SRS resources 00 1 01 2 10 3 11 4
[0281] The SRS resource selection information corresponding to the state can be configured / applied using MAC CE, and the like. In the case where a plurality of SRS resources are configured for the UE, a size of the TPMI can be configured / applied in a variable manner according to the configured SRS resource.
[0282] As described above, the UL DCI format configured / applied according to the number of SRS resources (and / or SRI field status) indicated via the SRI field can be exemplified as follows, and this can be linked / linked to the indicated SRS or can be linked / linked to the SRI by separate signaling. In addition or alternatively, at least part of the information signaled by the UL DCI format can be indicated by separate signaling.
1. Example of UL 1 DCI format [0283] UL 0 DCI format (maximum 30 bits) - the case where a single SRS resource (for the use of obtaining the UL CSI, for example, independently of the SRS feature (s) configured as the use of UL beam management (and / or for the use of DL CSI measurement) is
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[0284] - Single TPMI field (4 bits), [0285] - Single TRI field (2 or 3 bits), [0286] - RA, and / or [0287] - UL MCS, etc.
[0288] In this case, TPMI and TRI can be coded together.
2. Example of UL 2 DCI format [0289] UL 1 DCI format (maximum 50 bits) - the case where a plurality of SRS resources are configured [0290] - a plurality of TPMIs + TRI fields (for example example, 4 x N bits) (here, N can be the number of SRS resources configured (for example, for the use of obtaining UL CSI)) [0291] <case 1> - TPMI WB for each SRS + resource a single additional WMI TPMI (eg γ = aexptj #)) _for correcting TRI and / or inter-panel.
[0292] Case 1 is configured / indicated with each TPMI + TRI WB according to the number of ports in the configured SRS resource, and corresponds to the case where TPMI as the panel co-phase, and the like, described above , is additionally configured / indicated on the WB unit in order to be used for non-coherent / coherent JT, among others.
[0293] <Case 1A> - TPMI WB for each SRS + TRI + resource (TPMIs of the SB unit for inter-panel co-phase) [0294] Case 1a is configured with each TPMI + TRI WB according to the number number of ports in the configured SRS resource, and represents the case where TPMI as the panel co-phase, and the like, described above, is additionally configured / indicated on the SB unit (frequency selective pre-coding) in order to be used for non-coherent / coherent JT, among others. If the panel co-phase is configured with “SB unit”, a more accurate panel correction
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58/129 can be performed, but a larger TPMI field size is required.
[0295] <Case 2> - TRI + a single WMI TPMI + multiple SB TPMIs [0296] Case 2 corresponds to a double stage code dictionary (for example, the case in which it operates as the stage code dictionary double by grouping based on a specific property in the LTE DL Class A code dictionary and the single stage code dictionary (described below). In particular, Case 2 is configured with a single TPMI WB according to the total number of ports in the configured SRS resource, and corresponds to the case in which each TPMI for each SB is configured / indicated, Case 2 is appropriate for the case where each SRS resource or panel is well calibrated, such as the coherent JT.
[0297] <Case 3> TPMI WB for each SRS + TRI + resource (a single TPMI for inter-panel co-phase) + multiple SB TPMIs for a selected SRS resource (pre-selected by RRC or MAC CE or selected by SRI of the lowest index).
[0298] Case 3 corresponds to the case in which the TPMI WB is configured for each resource and for the corresponding additional TPMI (panel corrector). Performance can be maximized when it is configured / applied with the SB unit as in case 1a or case 2, but the configuration of the additional TPMI corresponding to the SB needs to be applied, and therefore the payload can be increased. Therefore, it is proposed that the cooperative transmission be performed only for the WB in a situation like the non-coherent JT, and the TPMI SB is transmitted only for a specific preconfigured SRS resource (or panel), recommended by the UE or configured by RRC, MAC CE, among others, or by the SRS resource (or panel) corresponding to the SRI of the lowest index.
[0299] <Case 3a> TPMI WB for each SRS + TRI + resource (a single TPMI for inter-panel co-phase) + multiple SB TPMIs for multiple resource
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Selected SRS [0300] FIG. 16 is a diagram illustrating the allocation of TPMI SB according to an embodiment of the present invention.
[0301] Case 3a corresponds to the case in which the TPMI WB and the corresponding additional TPMI (panel corrector) are configured for each resource in the double stage code dictionary structure. In order not to increase the TPMI for panel co-phase in the SB unit, it can be configured / applied in order to divide the SB into a plurality of sub-SUBs and correspond to different resources for each sub-SB, and for transmit the TPMI SB (to reflect the TPMI SB evenly for each resource), and this corresponds to FIG. 16 (a). As shown in FIG. 16 (a), all four SRS resources (SRS resources # 1 through # 4) are transmitted on each SB.
[0302] FIG. 16 (b) shows a modality of the SRS resource mapping for each SB index and SB TPMI transmission. As shown in FIG. 16 (b), if the number of SBs is greater than the number of SRS resources, first, the SB indices and SRS resource indices are mapped 1: 1 in ascending order, but the SRS having the resulting value obtained through modular operation between the target mapping index the number of SRS resources as their indexes can be mapped to the remaining SBs, which are not mapped, and the TPMI SB can be transmitted (for example, in In the case of the embodiment of Figure 16 (b), the SRS # 1 resource is transmitted).
[0303] FIG. 16 (c) corresponds to a modality in which an SB is allocated with a specific number of subgroups (for example, 2, this being configurable), and in the case where the number of SRS resources is greater than the number of subgroups (fourth line in the example), the TPMI is transmitted by all consecutive SBs. Even in this case, in order to transmit the TPMI to the entire SBs uniformly, the SB having an index exceeding (the number of
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SRS I the number of subgroups, 2 in the example) is mapped with the SRS feature through modular operation. For example, in the case of the embodiment of FIG. 16 (c), SRS resources 1 and 2 are transmitted to SBs 1, 3, 5, and so on, and SRS resources 3 and 4 are transmitted to SBs 2, 4, 6, and so on.
[0304] As another example, a method to reduce the granularity of the SB can be considered. In the method, for example, in the case of a system where the number of SRS resources is 2 and a single SB is 6 RBs, it is configured / applied so that a single SB is 12 RBs, and it can be configured so that the SB TPMI is transmitted on both of the two panels. When configuring this, there is the advantage that the TPMI SB's payload according to the multi-panel transmission may not increase.
[0305] As another example, one can consider a method in which the payload size of the SB TPMI is reduced through restriction / configuration to perform code dictionary subsampling or subset restriction in the transmission of multiple panels. In the case of code dictionary subsampling, the performance of the code dictionary may eventually deteriorate. Therefore, in order to minimize degradation, a UE can recommend so that the code word corresponding to a specific domain or direction is included for a gNB.
[0306] As another example, it can be configured / defined so that the UL 1 DCI format includes at least part of the following.
[0307] - SRI field (2 or 3 bits), [0308] - A single RI field (2 or 3 bits) / multiple RI fields (non-coherent JT case), [0309] - RA, and / or [0310] -UL MCS, etc.
[0311] In the present disclosure, several methods are proposed for
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61/129 transmission of TPMI (and / or Rl). In the event that all methods or the subset is used, gNB can indicate a method that is actually used for the UE either explicitly or implicitly through signaling.
[0312] The implicit indication method has the following modalities:
[0313] - The number of SRS resources configured (or activated): A UE can know whether to use a specific case of DCI format 0 or 1 according to whether the configured SRS is a single SRS resource or a plurality of SRS features implicitly.
[0314] - Parameters in relation to frequency selective pre-coding (eg ON / OFF, the number of SRS ports (the interpretation of a plurality of PMI fields can be changed according to frequency selective pre-coding) is automatically activated if the number of ports is X ports or more)): If the number of ports is X ports (for example, X = 4) or more, frequency selective pre-coding is considered , and a transmission method promised between case 2 to case 3 in advance or a configured transmission method can be used. In the case of X ports, it can be interpreted that a sum of all configured ports is X.
[0315] - The number of layers (DMRS port) or CWs (code words) (for example, two from Rl and MCS are transmitted, respectively, in the case of the 2CW interval): Since the case in which there are two MCSs is interpreted as the meaning of transmitting with non-coherent JT, the gNB can indicate a transmission method among the proposed methods 1 to 3 (promised in advance or pre-configured) to the UE implicitly. In the case of the 2 CW interval (for example, for the non-coherent JT, etc.) or in the case where the number of SRS resources is a specific number (promised in advance or configured) or greater, the load size useful for the indication of TPMI becomes greater, and in this case, frequency selective pre-coding can be disabled.
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62/129 [0316] In the case of the UL 1 DCI format described above, the coherent / non-coherent JT, etc., in which a plurality of SRSs are transmitted cooperatively, is described as a use case. In the case of coherent JT, due to the influence of the phase shift that occurred due to the phase shift differences of the UE oscillator, when the transmission timing interval for each resource is separated with a predetermined or longer time, there is a possibility that the TPMI corresponding to the panel corrector (phase and / or amplitude) does not operate properly. Therefore, in the case of carrying out / applying a cooperative transmission on a plurality of SRS resources for the purpose of coherent / non-coherent JT, a transmission time interval between the SRS resources may be restricted within a predetermined time. In the event that this is not done properly due to the capacity of the UE (eg, uncalibrated panel), the UE may report this as capacity information for gNB. In this case, it can be limited that only a single SRS transmission is configured / applied to the corresponding UE.
[0317] The method described above is exemplified with the case where RI and PMI are coded and indicated normally. However, for an efficient TPMI indication of the dual-stage code dictionary such as LTE DL, the method described above can also be applied to the case where RI and PMI are coded separately.
[0318] Hereinafter, a method of setting up a code dictionary assuming a single panel is described.
[0319] First, in the case of DFTs-OFDM, it is not necessary to support frequency selective pre-coding. Therefore, a single stage code dictionary is appropriate. In this regard, when designing a single-stage code dictionary, 2 ports and 4 ports in the EU LTE code dictionary can be used without any changes. The case of the 8-port code dictionary can
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63/129 be configured using the LTE UL 4-port code dictionary, and the mode is as follows:
[0320] 1. When v _4; is defined as a code word having the ^ith in UL 4 ports, the 8 port grade 1 code dictionary can be configured / 1 ^V U 1, R ⁷ ™. Ο τ Λ defined as v _8L * _{i + n} = - ^ =, ^ = exp (-----), n = 0, ..., Ll. The CARACTERISTICS
V2 | _ ^ v ₄ J l of this code dictionary is that it is configured based on the 4-port code dictionary, and more particularly, the 4 UL ports are applied to the 4 ports out of the 8 ports, and the 4-port UL codes apply the phase-shifted code word to the remaining 4 ports. At this time, the degree of phase rotation can be adjusted by the value of L. For example, when the value of L is 4, p degree of phase rotation can be configured with QPSK as Φ _η = {1,7, -1 , -j} or configured with its subset (for example, -1 or -j). At this point, the port 8 grade 1 code dictionary can be configured with 16 * 4 or 16 code dictionaries (in this case, this can be used for the purpose of tuning the number to the size of the 4 port code dictionary) , and in the event that a higher resolution is required, the higher value (for example, 8) can be set to the value of L. Such value of L can be configured by gNB for the UE.
[0321] In the case of the 8-port code dictionary, it is characterized by the fact that an implementation complexity of the UE is reduced using the same code word as the 4-port TPMI, and designed using the phase rotation value additional. This code dictionary can be applied in the same way as the double stage structure. For example, in the structure of W = W1W2 with W1 and the phase rotation value can be indicated by W2. In addition, this code word is suitable with X-pol (cross-polarized) antenna structure, and the 4-port code dictionary can be applied to the antenna port, W ₂ =), the 4-port code dictionary can be indicated
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64/129 configured with the same polarization.
[0322] In addition, once an antenna is placed in an arbitrary position on the UE, a loss of pass according to the position of the antenna port can be changed. In order to reflect this realistically, a code word can be configured by defining alpha, which is the power control part / time, except for the phase term in the code dictionary separately. Alpha can be defined / represented as a (e.g., cr and {1, VÕÃ Vú-25,0}), and this can be used as the PMI of W1. As a result, the final code dictionary can be defined as Equation 18.
[Equation 18] ¹ Γ ^v u ^V 8, L * i + n ^- I ------ Γ, '
Vl + to ² L ^at <4 ^V 4, / _ [0323] 2. As another method, the final code dictionary can be defined as Equation 19.
[Equation 19]
I v _B ^e í + j --- FI · 8is the tie size · code dictionary of v ₄ «and _f T. ^ ·} ^¥ 4 í 1 [0324] This code dictionary classifies the code dictionary of 8 ports in a 4-port unit (for X-pol, the same polarization unit), and is configured by applying different 4-port code words to each classified 4-port unit. In this case, a code dictionary payload size is set to 16 * 16 for grade 1, for example. In such a method to configure the codeword with the double-stage code dictionary, v _4i is designated as the WB code dictionary and used as v _{8Bi + y} = - ^ =
a code dictionary index is additionally reported with SB or shorter, and
8, Bi + j ~
can be configured.
Furthermore, since once antenna
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65/129 is located in an arbitrary position in the UE, the loss of pass according to the position of the antenna port can be changed. In order to reflect this realistically, a code word can be configured by defining alpha, which is the power control part / time, except for the phase term in the code dictionary separately. Alpha can be defined / represented as a (e.g., cr and {1.7 ^ 5, V0.25.0}), and this can be used as the PMI of W1. As a result, the final code dictionary can be defined as Equation 18.
[Equation 20] ¹ X ^V 8, Bi + / ^- I ------ Γ
Vl + cr ^ 4 ,.
[0325] In this code dictionary, in order to reduce the payload size of the code dictionary, only a part of the UL code dictionary of the
LTE can be used. For example, among the code word of degree 1, 16 to 23 (code dictionary outside the antenna) can be excluded. In addition, the principle can be applied identically to the other grade (for example, grades 2, 3 and 4).
In this case, the code dictionary can be configured / default using, zΡΖπη z> 1
Φ „= exp (——), n = 0, ..., Ll or v ^ _{1 + 7} = j = • ^(r) =
8, L * i + n. <R)
4, /, in the same way. Here, the superscript r indicates a degree. In addition, the proposed dual-stage code dictionary can be used for frequency selective pre-coding, and can be applied to CP-OFDM. Otherwise, you can restrict the single-stage code dictionary to be used for DFTs-OFDM and the dual-stage code dictionary to be used for CP-OFDM. It can be recommended by the UE as to whether to use the single-stage code dictionary and / or the double-stage code dictionary for gNB, or gNB can indicate to the UE by upper layer signaling (for example, RRC, DCI and / or MAC CE, etc.).
[0326] In addition, the 4-port code dictionary can be configured
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66/129. (1) with the structure v ^ * _{i + n} = φ „= exp (), n = O, ..., L-1 or v® _{s + J} = -Í y L. (1)
2, i (D
2.7 only for grade 1.
[0327] From now on, a code dictionary scheme for frequency selective pre-coding is proposed in the environment such as CP-OFDM, among others.
[0328] When it is assumed that the number of ports that the UE has in a single SRS resource is X, different delays are passed to each port X, and this can be understood as the phenomenon that the phase is shifted in the domain of frequency. The delay on the time axis is interpreted as a phase change on the frequency axis, and the phase change on the frequency axis can be represented as a function of frequency. For example, the phase change in the frequency axis can be represented as j ^ NKO) q _U j is an index corresponding to the corresponding frequency (e.g., subcarrier index, Physical Resource Block (PRB) (or group index of Pre-Coding Resources (PRG)), and SB index), and delta (^) is a coefficient that represents a phase shift in frequency.
[0329] In the present invention, a code dictionary is proposed for frequency selective pre-coding using the frequency shift phenomenon that occurs due to being subject to different delays for each UL SRS port.
[0330] The proposed code dictionary structure is as represented in Equation 21 for grade 1.
[Equation 21]
7Ã ^ex P (-J ² ^ i + A) y / Px-i exp (~ ^ kò ^ + ε _χ _ρ_ [0331] 'Indicates a relative beam power based on the first gate.
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This can be promised as a specific value, for example, pi = {1, 0.5, 0.25, 0}) in advance, or gNB can indicate to the UE via upper layer signaling (for example, RRC, DCI and / or MAC CE).
[0332] The variable for the phase shift value in Equation 21 can be defined as Equation 22.
[Equation 22]
3 = 3-, / = 1, ..., xi υη [0333] In Equation 22 the variables constructing ¹ can be defined as follows.
[0334] The value of ^r > can be indicated by upper layer signaling (for example, RRC and / or MAC CE), or a promised value / configured in advance can be used for numerology. For example, the value of ^r> can be set to the lowest value that satisfies '®' _in [128,256,512,1024,2048,4096]. _t ¹ e here, ^{cRB 50 is} the number of subcarriers in a Bandwidth (BW) configured for a CSI report. The value of is an oversampling value (the size of the Fast Fourier Transform (FFT)) and can be configured as a specific integer value (for example, 1, 2, 4, etc.) (This can have characteristics of a parameter irrelevant to a specific beam). The value of V can be configured according to numerology automatically, or gNB can be configured for the UE. Finally, Λ ¹ is a value in relation to the phase change speed in a configured BW λ for each port, and, for example, when ¹ = 2, this may mean that the phase of the Λ second port is changed as much as 4-fi on the configured BW. The value of ¹ can be set to a specific integer value (for example, 1, 2, 4, etc.), and gNB Λ can set it for the UE or the UE can select / assign the value from ¹ to Λ each beam in the set in which candidate values that can be the value of ¹ are included, and can return it to gNB.
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68/129 [0335] Equation 21 shows the calculated value assuming that there is a value corresponding to the maximum delay for each port. However, thanks to the multipath, if the delay spread is large, there may be restrictions when capturing all fluctuations of a channel in the frequency domain with a single signal sample in the time domain. In this case, there may be a method that captures a plurality of signal samples in the time domain (K samples, K can be configurable by gNB or recommended by UE (particularly, in the case of DL). So Equation 21 can be represented as Equation 23.
[Equation 23] [0336] In Equation 23, the subscript k index of each parameter can be understood as the k ' ^th sample determined by a rule promised in advance from the k' ^th largest time domain sample or maximum delay sample for each door. For example, if it is determined that K = 3, the FFT size is 64 and the maximum delay is 7 ^ (derivation), Equation 23 can be constructed using the 6 ^â , 7 ^ and 8 ^ (derivation) , sample in the K - K - - K time domain. In addition, gNB can be configured ^{1 -} χ-ι θ can indicate this for the UE. In the event that a correlation is small since the gap between the gates is large, the gNB can be set to ¹ , and indicate this to the UE by upper layer signaling.
[0337] When K = 1, Equation 23 can become Equation 21, and is described with Equation 21, for convenience of description.
[0338] The remaining parameters in Equation 21 can be
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69/129 defined / configured as follows.
[0339] The k index is an index value corresponding to a frequency, and configured according to a given subcarrier or an SB, and this is not additionally fed back. The value of ε _ι represents a phase shift value of | ' ^th port, and as in the example of ^ = {o _t l ±., 2 ±± _t ±±.} or ^. = (0, ^ 2 -, ... ^ 1-),
4 4 8 S can be indicated with a door unit additionally, with a value configured so that the phase shift for each beam has a value, such as QPSK, 8PSK, among others. In other cases, the phase shift is ignored, and the feedback overload can be reduced significantly by setting the value of ε _ι to zero.
[0340] In case of using the proposed method, the UE can calculate the SINR of the SB using a method, such as an average based on the TPMI applied with the RE level (for example), and report it to the gNB.
[0341] The most specific PMI operation for the UE is as follows.
[0342] First, a channel represented by each subcarrier (or PRB or SB) can be defined as H (&) and C ^NrxNt . Here, Nr and Nt represent Rx (or the antenna element, hereinafter referred to as the “antenna port”) of gNB and the Tx antenna port of UE, respectively. The UE can estimate the relative power indicator p _t , for PMI configuration, the phase change factor for each beam according to the frequency and the deviation ε _ι , using H (£) for each subcarrier. The gNB can indicate the factors that represent WB to the UE collectively or independently, and the UE can configure TPMI based on the information. Otherwise, gNB can indicate only a subset (for example, excluding the reactive power indicator /}, for TPMI configuration) of the factors for TPMI configuration for the UE, and the UE can configure the TPMI based on the information. At this point, it can be assumed that the remaining information that is not indicated is predefined (for example, /}, = 1).
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70/129 [0343] Hereinafter, a method of configuring the upper layer code dictionary using the method is described.
[0344] Generally, in the case of port X, assuming that gNB has more receiving antenna ports than UE, a transmission is available up to layer X, theoretically. Therefore, gNB can calculate an ideal parameter for each layer using a channel between the UE and gNB. That is, gNB can calculate ^{χ, £ χ} , and the like, independently for each layer. In this case, a final precoder ^x can be defined as Equation 24. In Equation 24,
R represents a transport layer.
[Equation 24]
7 / j ' ^ex P ( ^_ + ε ⁽ Ρ) ylp ⁽ xi exp (- + 4Ã)
[0345] In the code dictionary above, an independent PMI report is performed for each layer, and therefore there may be a problem that the payload size increases linearly as the layer increases. In order to solve this, for a specific link, the single stage, the double stage, or a specific code dictionary (for example, DL double stage code dictionary) can be used. In other contexts, using the orthogonal codes represented by the Walsh code, a code dictionary that is orthogonal to layer 2 can be constructed. In this case, all parts in relation to the relative power in Equation 24 can be set to 1. Then, the code dictionary for grade 1 and grade 2 can be constructed like Equation 25.
[Equation 25]
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exp (- j Ίπΐίδ ^ + ε) ¹ ') exp (- j ΖπΚδχI _x +
1 I exo (-, - <17,) expí'- í2.tã '<5V ,,. + ε ^ Ι,,) I. . 7 ', Γ .: _μ ^i; zn ^eC 4 = U <exp (-jΔΤ / ¾¾ + 1 - ^, expt, - j'2t.w + + ε '+ ·.) j <4, exp (- + ε ^ ί,) “4; exp (- j 2. ^, ½¾ ^ +)] [0346] Otherwise, in the case of the X-pol antenna, the code dictionary for grade 1 and grade 2 can be constructed like Equation 26.
[Equation 26]
Γ 1 Ί
exp (- j 2 ~ &<5 ^ + _, + ε ^ ζ_,) 1 ί ^{1 1} i ί exp (- + ^ D exp (-j2 ^^ ₃ + < ₂ _ _L ) I, ..
'Υϊ' = - ι ~ λ + i ^ef ->& = Ό
V2A I - $ sj i exp (-exp (- + ε ^ Ι. ^) J [0347] The phase correction term can be indicated by different values for each WB or SB (for example, mutually independent).
[0348] Hereinafter, the form of applicability of the proposed single panel-based code dictionary or the existing LTE LIL / DL code dictionary to multiple panels is described. Hereafter, for convenience of the description, it is assumed that the same number of antenna ports is provided for a single panel. That is, from now on, in case there are M panels, it assumes
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72/129 if there are N X-pol antenna port on each panel at each polarization. In the case of the code dictionary structure proposed below, the port selection functionality, and the like, can be processed by a separate signaling, such as SRI, and consequently, it is characterized by the fact that the selection of port and the like (eg example, if the code dictionary element is set to zero) in the code dictionary is not considered.
[0349] First, in the case of the X-pol (2-port) antenna configuration, it is assumed that the DL or UL 2-port code dictionary is used. In this case, the 2-door code dictionary can be constructed as follows. Since a group of beams is not necessary for 2 ports, W1 (2 by 2) can be assumed as an identity matrix, simply. In addition, the co-phase for each polarization can be performed for W2 (in the short term). That is, W2 can be built as W ₂ , a SB unit and / or
z = 1,2, and can be constructed by ^ = (1,7, -1, - /} or 8 PSKs.
Here, i can be a panel index.
In this case, the final code dictionary can be represented by the DL LTE code dictionary (assuming the QPSK co-phase).
[Table 12]
code dictionary index Number of1 layers20 i p Go J1Go Ί o '| _0 11 i Γ Vain 1 2 1 1 “1 -12 1Go _ 1"/ _ 2 1 1 j - j.3 1 Vain j _-
[0350] Using Table 12, the built-in code dictionary in which a plurality of SRS resources are combined can be represented as follows.
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73/129 [0351] For 4 ports, like the non-coherent JT, two antennas are provided for each resource (panel) 2 the 2-port code dictionary is used, and the phase between the resources (panels) and / or amplitude correction term can be considered. That is, this is represented by the mathematical expression, Equation 27.
[Equation 27]
w = W _n 'w ₂₁aW ₁₂ _AW ₂₂ _
[0352] Here, W _u eI ₂ , W ₂ ,
Φ „, and α, β represent amplitude correction and phase correction terms between resources (panels) (for example, a = {0, Vo.25, VÕ7,1}, / 7 = {1, j, - 1, - j}). α, β can be set / applied to either of the two values collectively («* β) for WB or SB. At this time, for efficient payload variation, different bit sizes (for example, WB = 2bits, SB = 1 bit) can be set / applied to WB and SB. In addition, an efficient application for each layer, such as a / 7 ¹ for grain, a , fp for degree, α, β can be applied independently for each layer. However, since the grade 2 configuration of the 2-port code dictionary has a structure in which the same beam is used for each polarization, in order to save the payload size, it may be preferred to use the same α, β. this can be applied in the same way as the code dictionary where the beam group W1 is configured with 1 beam, as well as the 2 port code dictionary.
[0353] As another mode, when configuring as «= {0,1}, it is possible to configure that an amplitude component performs only the panel selection function. In this case, since the size of the TPMI is changed depending on the value of alpha (that is, in the case where alpha = 1, the size of the TPMI is doubled), it may be preferable that the TPMI and the correction term e / or RI is coded together in the TPMI payload aspect.
[0354] The code dictionary is extended and applied to the 8-port code dictionary, which can be represented as Equation 28.
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74/129 [Equation 28]
w _n 'w ₂₁ ' w = at ₂ W ₁₂ âw ₂₂ (Z ₃ W ₁₃ / ₃ w ₂₃ « ₄ W ₁₄ _ _âw ₂₄ _
[0355] That is, each of the four features (panels) uses the 2-door code dictionary, and the correction term for each panel can increase according to the number of panels. In order to solve this, for the phase, through an operation such as β ₂ = β β ₃ = β β ^ = ft or β ₂ = β, β ₃ = 2β, β ^ = 3β, it can be configured / applied to be represented by a single value. At this time, the gNB can be configured for the UE in which the panel correction value is used, and since the panel correction value can be changed according to a UE antenna implementation, the UE can inform it through the gNB capacity report. The remaining elements of the 8-door scheme can be configured / applied in the same way as the 4-door case described above. The code dictionary normalization term can be calculated as 1 + oc ₂ + oc ₂ + oc _x [0356] Hereinafter, the code dictionary for the case where a single panel is configured with 4 ports (or the case in that the number of aggregate ports is 4 in the coherent JT situation). In the case of the 4-port code dictionary, when the dual-stage code dictionary is configured, the LTE-A Class A code dictionary can be extended and used or the Rel-12 eDL-MIMO 4Tx can be configured and used. In the case where the Class A code dictionary is used, the code dictionary structure can be limited to the structure in which W1 is configured with a beam (for example, represented as Config 1, etc.) in order to reduce the load TPMI useful value (eg SB payload size), and W2 can perform frequency selective pre-coding with the co-phase.
[0357] Table 13 exemplifies the 4-port code dictionary (4 ports
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75/129 of LTE DL).
[Table 13]
code dictionary indexNumber of layers 1 2 3 4 0 _{Mo =} [l -1 -1 -if rr · ¹ 'w ^ I4 ~ 3 34 _ο ^{! 1234!} /2 1 z / ι = [1 -j 1 IF / ¹ ' l ^ ^12} / 72 ^ ¹² / 73 F ^{! 1234!} /2 2 z / ₂ = [l 1 -1 f 1f ₂ ^{! 1)} w ^ ^U} I4i ¹² / 73 F ^{! 3214!} /2 3 f = [i J 1 ~ i ^T IF / ¹ ' WP ^} / J2 ¹² / 73 F ^{! 3214!} /2 4 «4 = [1 (-1-7) / 72 - j (1 - /) / 72 f IF / ¹ ' ^ ^14} / 72F ^{! 1234!} /2 5 m ₅ = [1 (1-7) / 72 7 (-1-7) / 72 ^ IF / ¹ ' ^ ^14} / 72F ^{! 1234!} /2 6 w ₆ = [l (1 + 7) / 72 -j (-1 + 7) / 72 ^ IF / ¹ ' ^ ^13} / 72F ^{! 1324!} /2 7 w ₇ = [1 (-1 + 7) / 72 7 (1 + 7) / 72 ^ IF / ¹ ' r ^ ^13} / 72 JF ₇ ^{134} / 73 F ^{! 1324!} /2 8 z / ₈ = [l -1 1 if IF / ¹ ' w ^ ^n} / 4iIF- / ¹²³⁴ '/ 2 9 ^u 9 = V -j - ¹ -jF 1F ₉ ^{1 'w: ^ / 4 ~ 310 // io = [1 1 1 -if F'o ¹ ' < ³ 7V2IF / o ¹³²⁴ 'Λ 11 // ii = [1 j -1 7'f F't ¹ ' IF / T ²⁴ '/! 12 _{M12 =} [1 -1 -1 if^ ₂ ^12} / 72ll-'A ¹²³⁴ '/! 13 // 13 = [1 -1 1 -if F ^! 3 ^1! < ^3} / 72FV ³²⁴ 'Λ 14 = 1 -1 -if Fl ¹ ' w '^ 141 < ² VV3 Fl ³²¹⁴ '/ 2 15 * 15 4 1 1 1F F ^! 5 ^1! w ^ ^} ! 4i < ¹² VV3 < ¹²³ 72
Η I Η [0358] In Table 13, ^w n = ¹ ~ ^2u n ^u n! ^u n ^u n | represents the matrix of
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76/129 4 χ 4 identity.
[0359] As another modality, there is a scheme for configuring a frequency selective pre-coding using the LTE DL single-stage code dictionary. In this scheme, the 4-port code dictionary of FIG. 13 is grouped in a unit of L indexes (for example, L = 2, 3, 4, and L is configurable by gNB or UE), and W1 is configured, and a beam selection can be selected via W2 (within group W1). For example, in the case where L = 2, the grade 1 code dictionary can be interpreted as
W = rjy ^{r} jy ^ír} | w = e ¹ L> ^{, + 1} J ' ² ₇ the information of a beam selection can be signaled additionally / independently. For example, the beam selection information can be signaled with L * 4 bits for the code dictionary or indicated together using the selected beams for permutation or combination to reduce overload, described below. In the dictionary codes and ec ^"] and a selection vector, and a vector whose single ^j-th element and" 1 "and the remaining elements are" 0 ". In addition, in the code dictionary, the superscript r corresponds to a degree.
[0360] The above modality is the scheme in which L beams are grouped according to a specific method, and the group index is selected / indicated with W1 and the beam selection / indication is carried out with W2. However, the modality proposed below is the scheme in which different indexes are allocated to each of the L beams, and the selected beam index is explicitly indicated (for example, for L = 2, the beam index (11, 5) Is indicated). In this case, the number of pc cases required for the indication can be ^{16 L '16 L} (permutation and combination). In the case of the number of cases calculated by a permutation operator, there is no ambiguity in the beam order that builds W1 between the UE and the gNB, but there is a disadvantage that the number of signaling bits increases. In the event that a grouping method constructed by a combination is used, it can be
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77/129 assume that the grouping is always arranged based on the low (or high) code dictionary index. In the case of not promised in advance as in the example, you can use pre-encoder cycling, such as semi-open loop (OL) for a fast UE, and it can be configurable which grouping method is used, and gNB can indicate it (or the UE can recommend it). The performance of frequency selective pre-coding through beam grouping has a major advantage in the aspect of signaling overload.
[0361] As another method, a method for grouping the Householder code dictionary 4Tx with L = 4 is as follows.
[0362] Table 13 is indicated by each code dictionary index and arranged as represented in Table 14.
[Table 14]
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index (k) ^ 0234} Degree 1 2 3 4 0 [bO b6 b5 b7] bO [bO b7] {14} [bO b6 b7] {124} [bO b6 b5 b7] {1234} 2 [b5 -b7 bO -b6] b5 [b5 -b7] {12} [b5 -b7 bO] {123} [b5 -b7 bO —b6] {1234} 8 [b6 bO -b7 -b5] b6 [b6 bO] {12} [b6 bO -b5] {124} [b6 bO -b7 -b5] {1234} 10 [b7 -b5 -b6 bO] b7 [b7 -b6] {13} [b7 -b5 —b6] {123} [b7 -b5 -b6 bO] {1324} 12 [b1 b2 b3 b4] b1 [b1 b2] {12} [b1 b2 b3] {123} [b1 b2 b3 b4] {1234} 13 [b2 b1 b4 b3] b2 [b2 b4] {13} [b2 b1 b4] {123} [b2 b4 b1 b3] {1324} 14 [b3 b4 b1 -b2] b3 [b3b1] {13} [b3 b4 b1] {123} [b1 b4 b3 b2] {3214} 15 [-b4 -b3 -b2 b1] -b4 [-b4 -b3] {12} [-b4 -b3 —b2] {123} [-b4 -b3 -b2b1] {1234} 1 [q ₀ jQi -q ₀ - Ml q « JQi ION] {12} [qo jqi ^- q »l {i 23} [q ₀ íqi qo - jqJ {1234} 3 [q ₀ - jqi-q ₀ jqj q « [q ₀ - jqJ {i 2} [qo ^- jqi ^- qo] {123} [-q ₀ - jqt Qo jqri {3214} 9 [qi jq ₀ qi jq ₀ ] qi [Qi jq ₀ ] {14} fai qi jq ₀ ] {i34} [qi jq ₀ qi jq ₀ ] {i234} 11 [Qi -jq ₀ qr jq ₀ ] qi íãi qj {l 3} fai qi ^- jqol {134} [qi qi-jq »- · ίίο1 {ΐ324} 4 [ ^β 0 í ^and i - j® /] ^and the í ^and o - jA] {i 4} [e ₀ ^and 3 - j ^and 2] {124} [e ₀ and ₃ ^- {123 4} 7 [e ₀ e ₃ - jtq je ₂ ] q> [ê ₀ -Kl] {13} [e ₀ - í ^e tj ^e ₂ ] {134} í ^and o - j ^and t ^and 3 j ^and ₂ ] {1324} 5 A - Joe The I laugh ₃ ] {i4} [θι e ₂ J ^e s] {i24} IA ^and 2 - í ^and o {123 4} 6 í ^and i ®2 J «-o - J] ^and i í ^e ti ^e ol {i 3} í ^e ij ^e o - J ^e 31 {134 _____________1____________ í ^e i je ₀ e2-je ₃ ] {i32 __________ 4} __________
[0363] The number in the bracket {} in Table 14 represents a position of the base vector / codeword selected from the base vectors / codewords. For example, in Table 14, {14} of degree 2 of the code dictionary index 0 can be interpreted for the first (bO) and fourth (b7) base vector / codeword among the base vectors / codewords. [bO, b5, b6, b7], [0364] The vectors represented in Table 14 can be defined as the
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Equation 29.
[Equation 29]
b «= T11 Λ = 111 , b ₂ = 11-1 , b ₃ = 1-11 , b ₄ = -111 b ₅ = 1-11 b ₆ = 11-11-1111-1-1
b ₇

[0365] Table 14 represents the mode in which it is grouped with code dictionaries having the same base vector / code word. For example, referring to Table 14, the dictionary indexes of codes 0, 2, 8 and 10 configured with the same base vector / codeword [bO, b5, b6, b7] can be grouped into a group. In case it is represented as Table 14, the LTE DL Householder 4-Tx code dictionary can be classified / grouped in the same base code word (evidently, through the phase or conjugate operation, different code dictionaries are applied ). In other words, the Householder 4Tx code dictionary can be divided / grouped into beam group 1 {0, 2, 8, 10}, beam groups 2 {12, 13, 14, 15}, beam groups 3
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80/129 {1, 3, 9, 11}, and bundle groups 4 {4, 7, 5, 6} based on the code dictionary index, as shown in Table 15.
[Table 15] ___________________________________
Bundle group 1 0, 2, 8, 10 Bundle group 2 12, 13, 14, 15 Bundle group 3 1, 3, 9, 11 Bundle group 4 4, 5, 6, 7
[0366] Therefore, the index allocated to each group of beams can be indicated by WB (and / or long term), and the optical beam in each group of beams can be indicated by SB (and / or short term).
[0367] The normalized term is not reflected in Equation 29. Normalization can be performed by multiplying
2 ^ R by the code word of each code dictionary index (corresponding to k and degree), here, 2 means each column normalization, Jr means normalization for each degree, and here, R represents a degree.
[0368] The code dictionary classification / grouping method can be classified / grouped according to the distance / degree of spacing between the doors (for example, classified / grouped according to the x value in the ^χ Ί port range) ). Otherwise, the code dictionary classification / grouping method can be classified / grouped according to the degree of granularity of the phase shift between the doors (that is, each of the classified code dictionary group may have different / split / independent phase) (for example, beam groups 1 and 2 are shifted with binary phase shift modulation (BPSK), beam group 3 is shifted with Quadratic Phase Shift Modulation (QPSK ), and bundle group 4 is shifted with 8-PSK), and, accordingly, the WB code dictionary is divided. Therefore, even in the case of the extended code dictionary in which a group of beams is extended according to the property, frequency selective pre-coding based on the
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81/129 codes can be performed. For example, in case the bundle group 3 is extended, that is, an example of a code dictionary to build a code dictionary replacing qO and q1 with q2 and q3 defined in Equation 30, respectively.
[0369] In the example above, the 2-bit signaling overhead for each of the WB and SB is required for indication of TPMI. Since grade 4 corresponds to the complete grade of 4TX, it can be pledged / configured to use an identity matrix ^ l ₄ in a simple way, or use a representative grade 4 code dictionary for each group. Otherwise, in order to reduce the signaling overhead for SB, a method of bundling the bundle group 1, 2, 3, 4 for L = 2 can be considered. For example, bundle groups 1, 2, 3, 4 grouped above can be classified / grouped into bundle groups 1, 2, 3, 4, 5, 6, 7, 8 (ie classified / grouped in code dictionary {0, 2}, {8, 10}, {12, 13}, {14, 15}, {1, 3}, {9, 11}, {4, 7}, {5, 6} , etc.), and in this case, the TPMI can be indicated by 1 bit for each SB.
[0370] As another grouping method, a grouping method can be proposed using a distance between the code words for each degree (rank) or degree of correlation. For this, as an example of a usable metric, the Cordal distance (d (A, B)) or matrix correlation (vector) (Corr (A, B)) can exist, and this can be represented by Equation 31.
[Equation 31] di A, Bj = - | U.4 ^h - 55 * | k ^ 2 *
C »rrU.B) = 145¾ [0371] Here, A and B are arbitrary matrices (vectors) having the same
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82/129 size, and the superscript “H” represents the transposition of the Conjugate (Hermitian), and II-tiF represents the Frobenius norm.
[0372] Using the metric, the example of code dictionary grouping of grades 1 and 2 in Table 13 can include Table 16.
[Table 161______________________________________________
Grade 1 Grade 2 Bundle group 1 0, 2, 9, 11 0, 3, 7, 11 Bundle group 2 1, 3, 8, 10 1,2, 8, 10 Bundle group 3 4, 7, 12, 15 4, 5, 6, 12 Bundle group 4 5, 6, 13, 14 9, 13, 14, 15
[0373] Each index in Table 16 corresponds to the code word index in Table 13. This is an example that the grouping is performed based on the degree of correlation between the code words. This may mean that the correlation between the TPMI WB-SB is maintained and frequency selective pre-coding can be performed in the event that a certain degree of correlation exists between the codewords. In addition, as shown in the example in Table 16, the bundle group can be different for each grade. This is due to the fact that the metric can be changed by the orthogonal beam included in W1, as the layer increases.
[0374] From now on, an overload reduction technique for TPMI is proposed.
[0375] - Proposal 1: Information on the grouping methods described above can be indicated by TPMI through DCI. However, in the aspect of overload reduction, the beam bundling method or the information of a beam group arbitrarily indicated from the gNB can be indicated through upper layer signaling, such as MAC CE, and the like, and the TPMI in relation to WB / SB can be indicated using the beams in the indicated / selected / chosen beam group through TRI and MAC CE as DCI.
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83/129 [0376] - Proposal 2: In the example above, the bit widths of the WB and SB are defined identically. In this case, a larger bit width is allocated to the WB than a bit width of the SB, but the SB is limited to a specific bit width (for example, 1 bit indication, etc.), and the overhead too can be decreased.
[0377] - Proposal 3: In the case of the report in the SB unit, the size of the TPMI becomes larger as the number of SBs increases. In order to solve this, it can be promised / configured in advance to subsample the transmission in SB mode. At this time, the subsampling information can be promised between the UE and the gNB in advance, or indicated to the UE through the upper layer like MAC CE, and the like, or the code dictionary subset restriction method that will be described below .
[0378] - Proposal 3-1: Since subsampling can significantly deteriorate UL performance, it can be promised / configured that subsampling is performed when the number of SBs that will be programmed for the UE is a specific N (for example , N = 3), but not performed in other cases.
[0379] The proposed method can be used / applied in order to reduce the overhead of UL / DL transmission based on the double code dictionary structure.
[0380] In the case where the TRI + TPMI is indicated with a single DCI and the size of the TPMI is changed depending on the TRI, in order to decrease the overhead, the TRI + TPMI can be encoded and transmitted together.
[0381] TPMI can be divided into TPMI1 (corresponding to W1) and TPMI2 (corresponding to W2) (hereinafter, generally called “TPMI1” and “TPMI2”). At this time, TRI / TRI + TPMI1 can be indicated by single DCI and TPMI2 (and / or the corresponding SB position information) can be indicated by MAC CE, and the like. In this modality, there is an advantage that the pre
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84/129 frequency-selective coding can be performed without large DCI signaling overhead, even if the SB pre-coding size is large.
[0382] Alternatively, on the contrary, TRI / TRI + TPMI1 can be indicated by MAC CE, and the like, and TPMI2 can be indicated by DCI. This mode can be beneficially applied to the case where the number of SBs is small (for example, 2) or RI or TPMI is dynamically changing relatively less than in the case of the WB transmission mode.
[0383] If indicated by the double DCI, the DCI can be configured / classified into 1 ^â DCI and 2 ^ DCI. In case the U DCI has a higher priority than the 2 ^ DCI and / or the 2 ^ DCI is indicated with a relatively long term compared to 1-DCI, the TRI can be included in the U DCI and separately coded for greater protection or jointly coded along with TPMI1 and TPMI2 2 may be included in DCI.
[0384] Information from TRI, TPMI1 and TPMI2 in relation to pre-coding can be interdependent, and therefore, even in the case where the UE is unable to decode at least part of the corresponding information, the UE can interpret / decode the indicated TRI, TPMI1 and / or TPMI2 based on the information received previously. Otherwise, as a standard behavior, a transmission with grade 1 and / or WB mode can be promised / configured in advance between the gNB and the UE.
[0385] In the case of the 8-door code dictionary, the 4-door code dictionary can be applied to each panel (feature), and the corresponding code dictionary structure is as represented in Equation 32.
[Equation 32]
w = W _n w ₂₁ - , W „= ^V 1 0 ’ and C ^4x2 , v, and C ^2xl , W ₂ , = '1«W ₁₂ _AW ₂₂ _0 ^V ! _
[0386] From now on, when transmitting the UL (or DL) in the very wide BW (for
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85/129 example, 40 MHz) in NR, the case in which frequency selective pre-coding is applied / performed is described.
[0387] Generally, in frequency selective pre-coding, when using the beam that existed in the W1 beam group (or with respect to the beam), a beam and co-phase selection in the SB direction are performed, in the structure of double-stage code dictionary. In the case of L beams that build a group of W1 beams, in order to reflect frequency selective pre-coding in the situation where the frequency selective property is dominant or in the situation where the BW is quite wide, it can be preferable to set the large L value. Therefore, the value of L can be configured according to / based on BW (for example, BW = ~ 10 MHz (L = 1), ~ 40 MHz (L = 4), etc.). In addition or as an alternative, the gNB can indicate the L value for the L value of the UE considering frequency selectivity, or the UE can recommend the L value that the UE prefers.
[0388] In addition to the code dictionary described above, it can be considered that another LTE code dictionary, for example, the Class A code dictionary, is used as the UL code dictionary. In this case, since the TPMI indicated by the DCI increases linearly according to the number of SBs, in order to restrict this, it can be limited so that only “Config 1” in which the SB payload size is the smaller is used.
[0389] For DFT-S-OFDM, in the case where TPMI WB is used for 2Tx, the grade 1 pre-encoder shown in Table 17 below can be used. In the following Table, the “code dictionary index” can be called “TPMI index” [Table 17]
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ft JLp; 5-1 ¹ »μ 1 * μ i §:
<3'-! 51 / - / 1; iiiiiolliiiii -áP®:
|; | ^ í:
) 5 iiiiiieliiiiii / [IFv i [0390] For CP-OFDM, TPMI indexes 0 to 3 for grade 1 and TPMI indexes 0 and 1 for grade 2 can be used. In addition, one of the two antenna port selection mechanisms can be supported.
[0391] - Alternative 1: In Table 17, the indexes of TPMI 4 to 5 for grade 1 and the index of TPMI 2 for grade 2 are used in CP-OFDM.
[0392] - Alternative 2: SRI indicates the selected antenna port.
[0393] For 2Tx, TPMI, SRI and TRI of Rel-15 they can be sent using the single stage DCI of the size that is configured in a semi-static way. The size of DCI included in TPMI, SRI and TRI does not change according to the allocation of PlISCH resources from the single-stage DCI. UE capacity can be materialized, which identifies whether the UE with UL MIMO capability can support coherent transmission through its own transmission chain.
[0394] For 4Tx of CP-OFDM, the following methods can be considered as a method of processing a port selection in a code dictionary.
1. Configurable code dictionary [0395] A. A dictionary of port combination codes and a dictionary of port selection codes are distinguished, and each can be signaled by an upper layer. That is, as the port selection code dictionary of the antenna disconnect function represented by the UL LTE code dictionary
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87/129 (or a subset of it) and the code dictionary represented by the DL NR Type I Household / CSI code dictionary, can be signaled by an upper layer like RRC to use a code dictionary among the code dictionary dictionaries. combination of port in which a non-zero coefficient exists on all ports is used. UEs configured with beam-conformed SRS (in case of extending to UL similar to eFD-MIMO LTE Class B) can use the port selection code dictionary.
2. Unique code dictionary [0396] A. This is a code dictionary represented by the union of a dictionary of door combination codes and a dictionary of door selection codes, as in case 1.
[0397] 3. When a code dictionary configured with methods 1 and 2 is used, TRI and TPMI can be coded independently or coded together. In the case where TRI and TPMI are coded together, in order to decrease the overhead of the DCI, a port selection is only allowed for a specific grade or less (for example, grade 1 or grade 2). In the case where method A is used, it is configured with the port selection code dictionary, and the TRI is indicated by 3 or 4, the UE can identify the indicated TPMI as the TPMI corresponding to grades 3 and 4 of the dictionary of port combination codes.
[0398] Hereinafter, in the case where the UL code dictionary described above is used (for example, pre-encoder cycling), a method is proposed to indicate a code dictionary subset restriction in gNB with the purpose of interference control. This can be used in order to decrease the signaling overhead of the upper layer signaling (for example, DCI). That is, this method aims to reduce the overhead in preparation for the case where the size of TPMI becomes larger due to the pre
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88/129 selective coding by frequency / operation of multiple panels, and the like, described above. Therefore, in this method, one can consider a case in which a code dictionary is reconstructed / subsampled as a code dictionary that includes a specific angle preferred by the UE, and domain. In this case, since the reconstructed and / or subsampled code dictionary size is smaller than the existing code dictionary, there is an effect that the payload size is decreased.
[0399] 1. Code word unit (beam): This is a method to indicate the complete code word by constructing the UL code dictionary with a scheme, such as a bitmap, for indicating the Specific Cell Reference (CSR). Therefore, the number of bits used for CSR is L1 + L2 + ... + LX. Here, Li is the i-layer code word number.
[0400] A. In the case where the 2D DFT-based code dictionary is used in CP-OFDM, the entire beam grid (GoB) can be indicated by a value of N1N2O102. Here, each of N1, N2, 01 and 02 is the number of antenna ports in the first and second domains and the number of oversampling.
[0401] B. CSR for a specific domain or CSR for a specific angle: For example, in the situation where the angular velocity for a vertical domain is very small, the code dictionary for the vertical component may have no influence on performance. The gNB can learn about it by measuring / monitoring a channel between the UE and the gNB, or the UE can recommend it for the gNB.
[0402] 2. Code Dictionary Config Unit: In case the UE uses a plurality of code dictionary configurations, the UE can recommend the preferred code dictionary or non-preferred code dictionary for gNB for the purpose of CSR.
[0403] 3. Grade unit: Upon receiving a CSR indication with a grade
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89/129 specific, the UE does not use the dictionary of codes corresponding to the corresponding grade.
[0404] A. For each grade, method 1 and / or method 2 can be combined with the CSR can be indicated. That is, for each grade, a beam / beam group (for example, thanks to the UE's coherent transmission capability, etc.) to which the code dictionary subset restriction is applied can be indicated independently. For example, in the case of the 2-port code dictionary as represented in Table 18 below, a bitmap of B_rank1 can be configured with 2 bits, and it can be promised / configured that, when the bitmap is "11", use the indexes from 0 to 5, and when the bitmap is "01", use the indexes 4 and 5. In addition, you can promise / configure that the 2 bit bitmap of B_rank2 uses code dictionary indexes from 0 to 2, when the bitmap is 11, and use only code dictionary index 2, when the bitmap is 01.
[Table 18]
[0405] In order to reduce signaling, a beam / group of beams can be indicated by a common encoding format, not a bitmap format. For example, bit size 1 is set for an indication, and it can be set that the bit indicates “01” in the example of the 2-bit bitmap, when the bit is “0”, and indicates “11” in the example 2-bit bitmap, when the bit is “1”.
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90/129 [0406] In the method, an independent indication for each degree is represented, but if the defined bitmap size is the same for each degree, all degrees can be restricted to a single bitmap (or that is, the entire degree constraint can be indicated using the corresponding bitmap).
[0407] 4. unit W2: In the case of the dual-stage code dictionary, a code dictionary such as a specific co-phase or LTE DL Class B, W2 corresponding to the code word W2, may be restricted in order to limit the use of a specific port. In this case, the UE can assume the restriction of grade 1 or the information corresponding to a grade can be indicated to the UE together.
[0408] 5. Panel unit: In the event that a panel indication is included in a code dictionary, with the aim of limiting transmission from a specific panel, gNB may indicate a restriction on a code dictionary usage corresponding to the panel specific to the UE with CSR (that is, indicates panel on / off with restriction of the code dictionary subset).
[0409] It is natural for gNB to report most of the CSR to the UE. However, during the process in which the UE performs the CoMP operation as JT or Joint Reception (JR), in the event that the beams for each panel interfere with each other, in order to control it, the UE may recommend the CSR of the proposed method for each gNB. As a more specific example, in the case where the UE is provided with two panels and the best corresponding Rx panel is different for each panel (in case a preferred panel / TRP is different for each panel), it is considered that a link between two panels / TRP and the UE has failed. That is, for example, when it is mentioned that a link between TRP1 and a panel of UE 1 is link 1 and a link between TRP2 and a panel of UE 2 is link 2, link 2 is considered to have failed. In this case, as an exemplary operation, the UE leaves link 2 and combines a port from panel 2 to link 1, and can
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91/129 if you consider the transmission to be more robust. In this case, when a beam transmitted in the existing TRP2 of panel 2 is used, interference with TRP2 can be considerably reduced, and therefore, when the panel is combined, the UE can recommend abstention / prohibition of the use of the corresponding beam. for gNB. This example can also be used even in the event of a link pair failure due to blocking, among others. That is, in order to reduce interference from another TRP / panel, the UE may recommend not to use the TPMI, digital and / or analog beam that interferes with another TRP / panel significantly.
[0410] In the case of 4Tx using broadband TPMI, at least one single-stage DCI can be used. For broadband TPMI and NR 4Tx code dictionary for CP-OFDM, one of the alternatives can be chosen.
[0411] -Alt 1: Rel-10 UL, possibly with additional entries:
[0412] - Alt 2: Rel-15 DL, possibly with additional entries:
[0413] - Alt 3: Rel-8 DL, possibly with additional entries:
[0414] NR supports 3 levels of UE capacity for UL MIMO transmission:
[0415] - Total consistency: All ports can be transmitted in a coherent manner.
[0416] - Partial coherence: Port pairs can be transmitted in a coherent manner.
[0417] - Non-coherence: No pair of ports can be transmitted in a coherent manner.
[0418] The TPMI code words of the code dictionary are used by gNB in a corresponding way.
[0419] For 1 SRS resource, [0420] - Total consistency: All ports corresponding to the ports in an SRS resource can be transmitted in a coherent manner.
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92/129 [0421] - Non-coherence: All ports corresponding to the ports in an SRS resource are not transmitted coherently.
[0422] - Partial coherence: The port pairs corresponding to the ports in an SRS resource can be transmitted in a coherent manner.
[0423] In addition to a code dictionary based transmission using an SRS resource, a code dictionary based transmission using multiple SRS resources including non-coherent inter-SRS resource transmission may be supported.
[0424] - Non-coherent inter-SRS resource transmission: Two DCIs can be used, and one TPMI per DCI can be used. In addition, a TPMI / TRI per SRS resource can be flagged, and the selection of multiple SRS resources can be indicated.
[0425] At least a single SRS resource is configured and for DFT-SOFDM, the additional 4Tx grade 1 code dictionary can be supported as shown in Table 19 below.
[Table 19]
mdíco do dífi · onári »> de cóíiiqss Layer ntimers «== l 16 - 23 rq ί o 12 1) | r-i ‘11 0 j -ri0 j W I m η0 i./ i oj 1 ¹ 1 I hi L ⁰ J M!2 0 (h i r ° i ri ί [ 0 [[-ri P]2 0 ( 1 o 11 1 i2 0 jL 24 -27 ' 1 j --______- 1ο ο L_________________________________J 1 Hi1 | o | 0 j 1 ’Olo |11o | 12. ’O] oj o [1! - - - -
[0426] For DFT-S-OFDM, the code dictionary of UL grade 1 LTE 4Tx for TPMI 0-15 can be supported. At this time, additional code words for antenna port selection can also be supported.
[0427] Considering the issues described above, the UE can report the
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93/129 additional capacity information in relation to coherent transmission to gNB. In this case, so that the gNB sets up a code dictionary for the UE, the capacity information can additionally be considered in addition to the antenna configuration information, antenna polarization, and the like, such as the antenna port number (maximum ) in a panel (or group of doors), the number of panels. These UE capacities can have different values depending on the implementation of the UE, and a lot of effort is needed to materialize them.
[0428] Therefore, the present disclosure proposes to report the UE code dictionary subset restriction preferred by the UE to gNB with capacity. Such UL code dictionary subset restriction may be the code dictionary to which the code dictionary subset restriction is applied to the code dictionaries described above. For example, the 3-bit capacity report can be presented as Table 20. Table 20 exemplifies the code dictionary subset restriction, and Table 21 exemplifies the 2-port code dictionary used to define Table 20.
[Table 20] _____________________________________________________
state Building the code dictionary 000 2 ports with TPMI indexes from 0 to 5 for grade and 0 to 3 for grade 2 001 2 ports with TPMI indexes from 4 to 5 for grade 1 and 3 for grade2 010 4 ports with TPMI indexes from 0 to 27 for grade 1 TBD for grade 2 to 4 011 4 ports with TPMI indexes from 16 to 27 for grade 1 TBD for grade 2 to 4 100 4 ports with TPMI indexes from 24 to 27 for grade 1 TBD for grade 2 to 4 101 Reserved 110 Reserved 111 Reserved
[Table 21]
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[0429] For a definition in Table 20, the 2-port code dictionary in Table 21 and the 4-port code dictionary that will be described below are used. The status "000" or "001" exemplifies a collective report for each grade. In case the capacity is indicated for each degree independently, the reporting field for each degree can be defined / configured independently.
[0430] Otherwise, in case the type of waveform in the supported code dictionary is different, a UE capacity can be reported with an independent capacity field (according to the type of waveform). In case the grade 1 code dictionary is the same, regardless of the waveform (for example, for 2 ports), the same grade 1 code dictionary is used regardless of the waveform, and therefore the capacity can be reported with the same state in the same field, and gNB can reflect this for all waveforms. For 4 ports, since different code dictionaries can be used for waveform, it may be preferable in terms of flexibility that the UE capacity is reported with an independent capacity reporting field.
[0431] As an alternative, the capacity field of the UE can be distinguished into independent fields according to whether it is TPMI of WB or TPMI of SB.
[0432] For greater flexibility, a method can be considered in which the
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95/129 UE capacity is indicated with the bitmap format. B_DFT-s-OFDM can be indicated with the bitmap (bitmap in relation to DFT-s-OFDM). For example, for 2 ports, it can be indicated by the 2-bit bitmap where 1 bit corresponds to the TPMI indexes from 0 to 3 and 1 bit corresponds to the TPMI indexes 4 and 5. For example, when the 2-bit bits is “11”, this indicates that the UE can use all TPMI indexes from 0 to 5 as the capacity of the UE, and when it is “01”, this indicates that the UE can use only the TPMI indexes 4 and 5 as the UE capacity, and a code dictionary can be built based on it. In addition, 4 ports, the capacity of the UE is indicated with the 3-bit 3-bit map. When the 3-bit bitmap is “111”, it indicates that the UE can use the TPMI indexes from 0 to 27, when the 3-bit bitmap is “011”, it indicates that the UE can use the TPMI indices from 16 to 27, and when the 3-bit bitmap is "001", this indicates that the UE can use the TPMI indices from 24 to 27.
[0433] For B_CP-OFDM, a bitmap for each degree can be added. The bitmap size for each grade can be different. That is, B_CP-OFDM can be constructed by joining each bitmap of degree. For example, B_CP-OFDM can be configured / indicated by the bitmap scheme such as {B_CP-OFDM_rank1, B_CP-OFDM_rank2, B_CP-OFDM_rank3, B_CPOFDM_rank4}, here, B_CP-OFDM_rank represents a bitmap for each degree. In case CP-OFDM and DFT-s-OFDM share the same code dictionary of grade 1, the UE can report the capacity with a single bitmap, ie B_CP-OFDM. Here, the capacity according to the number of ports can be reported with the independent bitmap, and the reported bitmap (more particularly, the number of independent bitmaps) can be configured according to the maximum port numbers. supported. For example, in the case of the maximum supported number of ports = 4, the UE can report the full capacity of the 2-port and 4-port code dictionaries, but in the case of the number of ports
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96/129 maximum supported = 2, the UE can report only the capacity for the 2-port code dictionary in bitmap format.
[0434] TRI in LTE can be indicated with a DCI of 5 to 6 bits being encoded together with TPMI. However, NR supports CP-OFDM, to indicate DMRS information, antenna port (s), scrambling identity and layer number can be indicated as Table 22 via DCI in relation to DL.
[Table 22] ________________________________________________________
A code word: Code word 0 enabled, Code word 1 disabled Two code words: Code word 0 enabled, Code word 1 enabled Value Message Value Message 0 1 layer, port 7, nSCID = 0 0 2 layers, ports 7-8, nSCID = 0 1 1 layer, port 7, nSCID = 1 1 2 layers, ports 7-8, nSCID = 1 2 1 layer, port 8, nSCID = 0 2 3 layers, doors 7-9 3 1 layer, port 8, nSCID = 1 3 4 layers, doors 7-10 4 2 layers, doors 7-8 4 5 layers, doors 7-11 5 3 layers, doors 7-9 5 6 layers, doors 7-12 6 4 layers, 7- doors10 6 7 layers, doors 7-13 7 Reserved 7 8 layers, 7-14 doors
[0435] Therefore, in the UL of the NR, similar to the information, the information of the antenna port (s), scrambling identity and layer number can be indicated in the DCI in relation to the UL. In this case, in the case of the UE that supports transmission based on UL code dictionary, an indication of the layer information (for example, information from the TRI) is superimposed, and therefore, the DCI can be wasted. Therefore, in the case where the information of the antenna port (s), scrambling identity and layer number is indicated in the DCI in relation to the UL, the TRI can be indicated with the field and the TPMI can be encoded with a single / independent and indicated field. At this point, once
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97/129 that the size of TPMI of grade 1 is the largest, the size of TPMI can be configured according to grade 1. A code dictionary is designed to correspond to the size of TPMI configured to the maximum for TPMI corresponding to grades 2 to 4, or, in the case where the TPMI number of the corresponding grade is less than the size of TPMI (for example, for grade 4 of the 4 ports, since it is total grade, the number of TPMI is approximately 1 to 3, for example, and in the case where the size of 1 TPMI is 5 bits), (32-3 =) 29 remaining states can be used for the use of error checking.
[0436] In the case where the transmission of UL based on the code dictionary is carried out from a plurality of SRS resources as described above, particularly, in the case of the non-coherent transmission represented by the non-coherent JT, several options may exist as described above, and these can be arranged like the example below:
[0437] Following are examples of execution of UL transmission based on code dictionary based on two SRS resources. Here, TPMIi and Trii represent TPMI and TRI r ^th SRS feature, respectively.
[0438] A. (SRI = 0) + (TPMI0) + (SRI = 1) + (TPM 11) + TRI: In this option, only one TRI is collectively indicated for two SRS resources, and TPMI can be indicated independently for each resource indicated by each SRI.
[0439] B. (SRI = 0) + (SRI = 1) + TPMI + TRI: This option represents the case where the SRS ports on the two SRS resources are aggregated and transmitted using a single TPMI, and here, the TRI can be indicated as single.
[0440] C. (SRI = 0 + TPMI0 + TRIO) + (SRI = 1 + TPMI1 + TRI1): This option follows the option of A, but corresponds to the case in which the TRI is indicated for each resource.
[0441] As indicated above, the TRI can be indicated in the DMRS table.
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When option A is used, the TRI can be interpreted to the full extent that the UE performs the UL transmission. At this point, in the event that a layer is indicated using a plurality of resources, it may be ambiguous that the layer number is indicated / mapped to a certain resource. For example, in case the transmission of UL is performed in two resources, the total grade is 3 and is indicated in the DMRS table with TRI = 3, it can be ambiguous if the grade transmitted in each resource is (TRIO, TRI1) = ( 1.2) or (2.1). Therefore, an additional indicator (for example, 1 bit indicator) to clarify it can be used / defined. In addition, or alternatively, if indicated by a specific TRI (for example, TRI = 3), the degree to which the corresponding resource (s) is (are) transmitted in the SRI field. For example, when the total grade is 3, it can be promised between EU and gNB that the resource for grade 2 transmission is always indicated first. That is, as shown in Table 23 below, in the case of TRI = 3, the state “01” means that the 0 = ^^ resource is grade 2, and “10” means that the first resource is grade 2.
[Table 23] _______________________________________
state Number of SRS resources 00 0 01 0.1 10 1.0 11 0,1,2,3
[0442] Even in the case where TRI = 1, similar to the case where TRI = 3, the fact that the resource in which grade 1 is transmitted can be indicated explicitly with an additional indicator or indicated implicitly. Otherwise, in the case where TRI = 1, since grade 1 transmission is performed on only one resource, only a single resource can be indicated in the SRI state.
[0443] In the case where TRI = 1, grade 2 transmission is performed on the only selected resource, or grade 1 transmission can be performed on each of the resources. In the first case, like grade 1, in the SRI state, only one resource (the
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99/129 selected resource in which grade 2 transmission is performed), and in the latter case, grade 1 transmission is understood to be performed on each resource, and therefore there is no ambiguity.
[0444] In the case where TRI = 4, it can be understood that each resource performs grade 2 transmission.
[0445] This example represents the case, the case where the number of ports used for total UL transmission is 4, two SRS ports are provided for every two resources, respectively.
[0446] In case the number of ports used for total UL transmission is 4 or more, the case is described in which the transmission of coherent / non-coherent UL is performed through two resources, and four SRS ports are used for each resource, for example. In addition, in this case, the degree of total transmission is assumed to be 4. Then, in the case of non-coherent transmission, the degree for each resource can be indicated unambiguously with the option / method proposed up to the case TRI <= 3. However, in the event that it is indicated by TRI = 4 and grade 4 transmission is performed on a resource, the SRS resource transmitted in the SRI field is indicated separately, and, consequently, the ambiguity can be removed. However, since there may be ambiguity as to whether (TRIO, TRI1) = (1.3), (2.2) or (3.1) may have existed, an indicator to distinguish it can be flagged separately. Otherwise, the total TRI can be indicated in the DMRS table, and the TRIi transmitted in each resource can be coded together with TPMI in the TPMI field and indicated. That is, the DCI can be configured with at least one of the following.
[0447] - SRI [0448] - A TRI incorporated in the DMRS [0449] - TPMIi + TRIi for each i-th SRS resource [0450] In the case of a transmission using a plurality of
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SRS and in the case where each of the TPMI for each resource and / or TRI is indicated, a TPMI (and / or TRI) field can be encoded in such a way that a plurality of TPMlis (and / or TRIis) for each resource is concatenated , and in the case where the encoded size is unable to fill the entire payload size of a given field, the remaining bits can be filled with zero. In this case, the UE does not expect the total TRI value to be different from the sum of all TRIis indicated by the seventh SRS resource in the TPMI (and / or TRI) field. That is, one must satisfy that TRI = TRIO + TRI1 + and so on.
[0451] Using the method above, DCI decoding can be performed in an order: DMRS -> TPMI field.
[0452] As proposed above, in the case where the TRI is incorporated in the DMRS table, an indicator for TRI is not necessary. Therefore, only TPMI is used, and the number of code words is not significantly restricted to the higher grade, as the DCI overhead is reduced, and therefore, the performance of the higher grade can be improved.
[0453] One of the other methods to reduce the burden of DCI, one can consider a method in which the TRI and the TPMI are coded together and included in a single field, and the DMRS table (Table 24 below) is interpreted by the IR indicated in the field.
[0454] For example, it is assumed that the DMRS configuration shown in Table 24 is used for UL code dictionary-based transmission. In this case, as a group of doors, as shown in Table 24, each of the indexes from 0 to 5 for grade 1 transmission (single grade), indexes from 6 to 9 for grade 2 transmission, index 10 for grade transmission 3, and index 11 for grade 4 transmission, can be used. Consequently, a maximum width of 3 bits of the DMRS field is required (since the index corresponding to grade 1 is 6, which is the largest). This can have an effect of reducing the
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101/129 size / width up to 1 bit compared to the case where the bit / width size of the existing DMRS table exemplified in Table 24 below is used without any changes, not reduced (ie, the 4-bit DMRS field is used without any changes, all 11 indexes are flagged).
[0455] As proposed above, by the TRI indicated in the TRI + TPMI field, the state of the 3-bit DMRS field can be reindexed for each degree as represented in the 4- column of Table 24, and the UE can reinterpret the DMRS table (for example, Table 24) based on the indicated TRI. For example, in the case where TRI = 2 (grade 2) is indicated in the TRI + TPMI field and status 1 (ie reindex value “1” in Table 24) is indicated in the 3-bit DMRS field, the UE can understand / identify that the index “7” is indicated in the DMRS table of Table 24. In addition, the UE does not expect the UE to be indicated with a state that exceeds the index range of the DMRS table in which an indicator indicated in the field 3-bit or did not exist. For example, in the case where the UE is indicated with TRI = 2, the UE does not expect the UE to be indicated with status 5 in the 3-bit DMRS field.
[0456] According to this modality, DCI decoding can be performed in the order: TRI + TPMI -> DMRS field.
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102/129 [0457] The following alternatives can be considered in order to project it in the direction of increased granularity or flexibility of selection of the code dictionary to the maximum according to the size of TPMI.
[0458] For broadband TPMI, for the NR 4 Tx code dictionary for CP-OFDM:
[0459] Alt 1: Rel-10 UL, possibly with additional entries:
[0460] Alt 2: Rel-15 DL, possibly with additional entries:
[0461] Alt 3: Rel-8 DL, possibly with additional entries.
[0462] For example, since Alt 1 uses the UL code dictionary without any changes, in the case of grade 1, one can consider using the code dictionary (for example, Table 19) proposed above without any changes . Then, the total TPMI size becomes 5 bits, and a maximum of 32 codewords can be considered for each grade.
[0463] Then, the code dictionary for grade 2 can be defined as Table 25.
[Table 25] ___________________________________________________
code dictionary index Number of layers u = 2 0-3 τ ⁰ 1 Γ1 οΊ Γ 1stΓ 1st)1 1 o 1 1 0 1 -J 01 -J 02 0 1 2 0 1 2 0 12 0 1L ° L ° J L ° ¹ L ° 4-7 Γ ¹ ο Ί Γ1 o] Γ1 o “Γι ο Ί1 -1 0 1 -1 0 1 J 01 J 02 0 1 2 0 1 2 0 12 0 1L ° L ° J | _0 1| _0 -1_ | 8-11 Γ1 o] Γι ο Ί O i oΓ ¹ ο Ί1 0 1 1 0 1 1 0 11 0 12 1 0 2 1 0 2-102-10| _0 1_ | | _0 -1_ | L ° ¹ L ° -d 12-15 Γ1 o] IT ο Ί Γ1 o ’Γ i ο Ί1 0 1 1 0 1 1 0 11 0 12 0 1 2 0-1 2 0 12 0-11 0 1 0 -1 0-1 0> - - > - - > - - > - -
[0464] The code dictionary indexes from 0 to 15 defined in Table 25
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103/129 is a code word (ie, partial-coherent code word) that is appropriate when partial-coherent transmission is performed, in which four ports are paired with two and transmitted.
[0465] Else, in the case where 16 code words are added, the combination as shown in Table 26 can be derived.
[Table 26]
Index of Number of layers ^υ ~ 2 dictionary of J codes 16-19 12 ^ 2 '1 1 ’1 11 -11 -112V2 '1 1 ’1 1j -JJ -j_12J2 '1 1 ’j j 1 -1J -j_12V2  1 1 ’j jj -J-1 120-23 12 ^ 2  1 1-1 -11 -1-1 112J2 1 1-1 -1j -J-J j12V2 1 1-J -J1 -1_-J j12V2  1 1 ’-j -Jj -J1 -124-27 2 1 0 ’0 10 00 0J_ 2 '1 0 ’0 00 10 02 '1 0 ’0 00 00 1J_ 2 '0 0 ’1 00 10 028-29 2 0 0 ’1 00 00 1J_ 2 '0 0 ’0 01 00 1
[0466] The code word of the code dictionary indexes 16 to 32 is the port combination code word (ie, full coherence code word) that uses all four ports, and a part of the code dictionary LTE or NR DL, and the code word from the code dictionary indexes 24 to 29 is the code word (ie, non-coherent code word) that is appropriate when all four ports perform non-coherent transmission. As such, in the case where TRI and TPMI are normally configured, the granularity of the TPMI is decreased as it goes to the highest degree considering the total payload, but in the case of the
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TRI is indicated in the separate DMRS field, there is the advantage that the code dictionary can be configured more abundantly, even to the greatest degree. That is, in connection with the consistent transmission of the UL TX port, more code words are allocated for partial transmission and the like, and this can be useful to increase the performance of the UE having the corresponding capacity.
[0467] Likewise, in the case of grade 3, a code dictionary can be configured with Table 27.
_______ [Table 27] _________________
code dictionary index Number of layers ^υ ~ 3 0-3 2 T o o1 0 00 1 00 0 12 ‘1 00’-10 00 1 00 0 12 T 0 0 ’0 1 01 0 00 0 12 "1 00"0 1 0-10 00 0 14-7 j_2 T o o0 1 00 0 11 0 0j_2 ’1 0 0“0 1 00 0 1-10 0j_2 '0 1 0 “1 0 01 0 00 0 1j_2 "0 10"1 0 0-10 00 0 18-11 j_2 '0 1 0 ’1 0 00 0 11 0 0j_2 ’0 10’1 0 00 0 1-10 0j_2 ’0 1 0’0 0 11 0 01 0 0j_2 "0 10"0 0 11 0 0-10 0code dictionary index Number of layers ^υ ~ ³ 12-15 1 2χ / 3 T 1 11 1 -11 -1 11 -1 -11 2a / 3 '11 1 ’1 1 -1 j -j j _j -j -j.12V3 "11 1’j j -j1 -1 1J -j -j_1 2V3 1 1 1 “j j -jj -j j-1 1 116-19 2 1 0 0 ’0 1 00 0 10 0 0J_ 2 Ί 0 0 ’0 1 00 0 00 0 12 1 0 00 0 00 1 00 0 1J_ 2 "0 0 0’1 0 00 1 00 0 1
[0468] In this table, the codeword indices 12 through 15 are port combination codewords that use all four ports, and a portion
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105/129 of the LTE or NR DL code dictionary, and an example of a code word (ie, full coherence code word) that is appropriate when four ports are transmitted coherently. Code word indices 16 to 19 are an example of a code word (ie, non-coherent code word) that is appropriate when all four ports are transmitted in a non-coherent manner. In addition or as an alternative, in this table, code word indexes 0 to 11 are an example of a code word (ie, partially coherent code word) that is appropriate when four ports are transmitted in a partially coherent way. At this time, switching off the antenna is considered for the power scaling factor, and as another scaling factor, for example, it can also be considered. In addition to the example, in order to increase the granularity of the remaining states, a part or all of the Household LTE DL Rel-8 code dictionary can be included / used.
[0469] An example of a Grade 4 code dictionary is as shown in Table 28.
[Table 28]
code dictionary index Number of layers ^υ ~ ^ 0-3 2 ’1 0 0 0’0 10 00 0 100 0 0 14 11 1 1 ’11-1-11-11-11-1-1 14 Ί1 1 Γ 11-1-1 j -j j -j J -j -j j.4 11 1 1J J -J -J 1-11-1_J -J -J J _4 4 1 1 1 1J J -J -JJ -J J -J-11 1-1
[0470] In this table, codeword indices 1 through 4 are port combination codewords (that is, full coherence codewords) that use all four ports, and a part of the LTE or NR code dictionary DL, and an example that four ports are transmitted coherently. In addition to the example, in order to increase the granularity of the remaining states, a part or
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106/129 the entire Household LTE DL Rel-8 code dictionary can be included / used. Particularly, since grade 4 is full grade transmission, it is anticipated that performance may not be improved to a large extent, even in the case of increased granularity. Therefore, in order to reduce the complexity of the UE, it can be configured with a specific number (for example, 3) of code words (for example, configured with 0, 1 and 3 code words).
[0471] In the case of the 4Tx code dictionary for CP-OFDM, the TPMI payload can be changed due to the code dictionary subset restriction indicated by the coherence capability report (for example, full coherence, partial coherence and not -coherence) of the UE or upper layer signaling. At this time, in the case where the TRI and the TPMI are coded together, the effect of reducing the payload may correspond to the case in which the sum of the TPMIs for each degree according to each coherence capacity is decreased. In the case where the TRI and TPMI are coded separately, the maximum value of the TPMI size for each grade should be decreased to reduce the TPMI payload. Therefore, it is proposed to restrict the maximum TPMI size according to each coherence capacity. For example, the following example can be considered.
1. Total consistency - 5 bits [0472] 1-1. For grade 1, a code dictionary can be defined as shown in Table 29.
[Table 29]
0-71 1 1 1 1 1 1 1 1 11 11 11 11 j1 j1 j1 j 2 12 j2 -12 - j2 12 j2 -12 - j -1 j 1 - j j 1 - j -18-151 1 1 1 1 1 1 1 1 -11 -11 -11 -11 - j1 - j1 - j1 - j 2 12 j2 -12 - j2 12 j2 -12 - j 1 - j -1 j - j -1 j 1
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index d «dictionary cfe codes Cam number adas y- 1 i 1 i1 i i ¹ i i 0!Γθ! i 0: liei laughs 0 i I δ i 1 í § i 1 h i 11 id 1 i 1 i 1 i 1 i 1b — 2.3 · -: __________:>______! '_______________ 1 ·: 2 i 1 j 2 _: 0 ϊ 2 | 0 [ 2 ; 0 i 2 ; δ; i 0 i : Λ: 0 í; ΐ i i-li ! f i L '* __ _Γ1; Γ · ο i 0 i TCH 1 1 0 i ihi i 0 i I Ó È 24 -27 -! - 1 1 - - 2 0 · § 2 cq 2 1 i; 2 | 04id 0 ’ I i - 1- - - -> 1- -
[0473] In order to fill 32 states additionally in Table 29, when considering 8 PSK with the phase of each of the elements, the code word as represented in Equation 33 can be additionally considered.
[Equation 33]
1111"1-71 +. /-i +. /-1-7THE _ V2a / 2 _ V2 ^and the - -j ^and the - j ^and i - -j ^and i - j-1-7-1 +. /1 +. /1-7L V2 JL V2 JL VIJL vi J
[0474] 1-2. For grade 2, the code dictionary can be represented in the
Table 30.
[Table 30]
dictionary indexcodes Number of layers ^ = 2 0-3 22 T o1 00 1-J.2 T o1 00 1j.2 1 0 ’-J 00 10 122 1 0 ’-J 0 0 10 -14-7 j_2 1 0-1 00 1_ ° -Jj_2 ’1 0’-1 00 1_ ° Λj_2 T o ’J 00 10 12 2 T o ’J 0 0 10 -18-11 22 T o0 11 00 1j_2 T o0 11 00 -1j_2 ’1 0’0 1-1 00 122  1 0 ’0 1-1 00 -1
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12-15 2 T 0 ’0 10 11 02 ’1 0’0 10 -11 02 ’1 0’0 10 1-1 02 1 0 '0 10 -1-1 016-19 1 2> / 2 T 1 "1 11 -11 -11 2V2 "1 1"1 1 j -j1 2V2 "1 1" j j1 -11 2> / 2 "1 1 j j j -j -1 120-23 1 2V2  1 1-1 -11 -1-1 11 2> / 2 1 1-1 -1j -j-J J1 2> / 2 1 1-j -j1 -1 j1 2> / 2  1 1 ’-j -jj -j1 -124-27 J_ 2 1 0 '0 10 00 0J_ 2 '1 0'0 00 10 0J_ 2 '1 0 ’0 00 00 1J_ 2 0 0 ’1 00 10 028-29 J_ 2 '0 0'1 00 00 1J_ 2 '0 0'0 01 00 1
[0475] In addition and / or alternatively, as another example, a code dictionary can be configured by selecting four (for example, 24 to 27) from the code word indexes 24 to 29 of the grade 2 code dictionary of Table 30 above. Then, the four additional states to adjust to the 5-bit size can be configured as represented in Equation 34 or can be selected from eight states defined in Equation 35.
[Equation 34]~ 1 -1 + 7V21 -71 1 + 7721 7 1 hJ_ -J 1 1 + 7V2 -1 + 772 1 -1 + 772 7 1 -1 + 7 λ / 2 1 + 7V2 2 ^ 2 -j -1-7 2- ^ 2 7 1 2V2 7 1-772 2V2 -7 1-1-7 1-1 + 7L 72 1-772 _1-7_ 72 11 + 7a / 2 1-7V2 _
[Equation 35]
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[0476] In addition or alternatively, all used but 12 code words (for example, # 0 eight 8-PSK grade 2 are to # 11 code dictionary / code word) are selected from code dictionary # 0 to # 15, and a total of 32 states can be configured.
[0477] 1-3. For grade 3, the code dictionary can be represented in
Table 31.
[Table 31]
code dictionary index Number of layers 0-3 2 1 0 0 ’1 0 00 1 00 0 12 ’1 0 0-10 00 1 00 0 12 ’1 0 0’0 1 01 0 00 0 12 ’1 0 0’0 1 0-10 00 0 14-7 J_2 1 0 0 ’0 1 00 0 11 0 0J_ 2  1 0 0 ’0 1 00 0 1-10 0J_2 ’0 1 0’1 0 01 0 00 0 1J_ 2 0 10 ’1 0 0-10 00 0 18-11 J_2 0 1 0 ’1 0 00 0 11 0 0J_ 2 0 10 ’1 0 00 0 1-10 0J_2 ’0 1 0’0 0 11 0 01 0 0J_ 2 0 10 ’0 0 11 0 0-10 012-15 12λ / 3 11 11 1 -11 -1 11 -1 -112 ^ 3 Ί 1 1 ’1 1 -1 j -j j _j -j -j.12 ^ 3 11 1 ’j j -j 1 -1 1J -j -j.12V3 1 1 1j j -jj -j j-1 1 1
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to 27 defined in Table 31 can be replaced by at least part of the code dictionaries in the form as shown in Table 36 below.
[Equation 36]
The transmission corresponding to each antenna port is the same when it is observed as the sum (= 0.25) of each layer, and the entire antenna port is transmitted through the first layer, and only a specific group of ports is
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111/129 transmitted through the second and third layers, and it can be seen that it has the property of port selection and port combination appropriately.
[0480] 1-4. For grade 4, the code dictionary can be represented in Table 32.
Layer 2 transmission is performed on two panels for code words 4 through 7. That is, Table 32 represents a code dictionary for the transmission of layer 2 from each of the antenna ports {1, 3}, { 2, 4}, and can be used to cover the multi-panel code dictionary.
[0482] Generally, as the layer increases, the gain obtained from the granularity of the code dictionary is not so great. For example, in the case of total grade transmission, the case of grade 4 transmission may present the performance that is not so far behind when compared to the case where several code dictionaries are used, even in the case of only 1 or 2 dictionaries of code. codes to be used. Therefore, in the case where a code dictionary is configured with a combination or subset of
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112/129 proposed codes, not all the configured TPMI size (5 bits for the mode) can be used as the layer increases, and the bit / state that is not used can be used for error detection. In addition, there is the advantage that the complexity of the TPMI calculation decreases as the bit / state decreases in the aspect of the gNB.
2. Partial coherence - 4 bits [0483] A partial coherence code dictionary can be configured with at least part of the code words (ie, partial coherence (transmission) code word, non- coherence (transmission)) being selected, except total coherence transmission coherence in the proposed total coherence code dictionary. For example, the partial coherence code word can be configured with index code words 16 to 27 for grade 1, index code words 0 to 11 and 28 to 31 for grade 2, index code words 0 to 11 and 28 to 31 for grade 3, and index code words 4 to 12 for grade 4, in the proposed total coherence code dictionary. In this case, the maximum number of codewords is 16, and 4 bits can be allocated.
3. Non-coherence - 2 bits [0484] The non-coherence code dictionary can be configured with at least part of the code words (that is, the non-coherence (transmission) code dictionary) being selected, except the total (or partial) coherence (transmission) code dictionary in the proposed full (or partial) coherence code dictionary. For example, the non-coherence code dictionary can be configured with index code words 24 to 27 for grade 1, index code words 28 to 31 for grade 2, index code words 28 to 31 for grade 3, and index code words 12 for grade 4, in the proposed total coherence code dictionary. In this case, the maximum number of codewords is 4, and 2 bits can be allocated.
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113/129 [0485] That is, summarizing the content described above, the full coherence code dictionary can be configured with the full coherence transmission code dictionary, the partial coherence transmission code dictionary and the code dictionary transmission of non-coherence. The partial coherence code dictionary can be configured with the partial coherence transmission code dictionary and the non-coherence transmission code dictionary, and the non-coherence code dictionary can be configured with the transmission code dictionary. non-coherence.
[0486] Therefore, UL code dictionary types can include full coherence code dictionary, partial coherence code dictionary and non-coherence code dictionary, and UL code dictionary (ie, the total coherence code dictionary) can be configured with the total coherence (transmission) code dictionary, the partial coherence (transmission) code dictionary and the non-coherence (transmission) code dictionary.
[0487] In the present disclosure, a code word can be called a "pre-coding matrix".
[0488] In case the DFT-s-OFDM and CP-OFDM are configured with separate DCI formats, the proposal can be applied to the DCI format configuration for CP-OFDM. In the event that DFT-s-OFDM and CP-OFDM support dynamic switching, it may be preferable for the DCI bell scheme to be an integrated scheme in a waveform. Therefore, in case the CPOFDM is changed to DFT-s-OFDM, the fields indicating information, such as antenna port (s), scrambling identification and layer number, can be interpreted by Table 3 in a modifiable way in the DCI related to UL. Table 33 is a table of the mapping of a cyclic deviation field in the DCI format related to UL for ^DMRSÁ and ^{(<)) w} .
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114/129 [Table 33]
Cyclic Deviation Field in DCI format related to uplink [3] z. = o ιιιιβlllll iiiiiiiiiiiilllllΙΙβΗΙΙΙΙ iBiilllllllilll | illilillll 000 0 6 3 9 [1 1] [1 1] [1 -1] [1 -1] 001 6 0 9 3 [1 -1] [1 -1] [1 1] [1 1] 010 3 9 6 0 [1 -1] [1 -1] [1 1] [1 1] 011 4 10 7 1 [1 1] [1 1] [1 1] [1 1] 100 2 8 5 11 [1 1] [1 1] [1 1] [1 1] 101 8 2 11 5 [1 -1] [1 -1] [1 -1] [1 -1] 110 10 4 1 7 [1 -1] [1 -1] [1 -1] [1 -1] 111 9 3 0 6 [1 1] [1 1] [1 -1] [1 -1]
[0489] In Table 33, since lamda is a parameter in relation to a degree, only the column for lamda = 0 can be applied to DFT-s-OFDM.
[0490] In the code dictionary, a power scaling is configured assuming the antenna is switched off. That is, when a transmission power from the UE at a given power is designated as P, the power is distributed evenly to all ports, and a transmission power from each port is given by P / N (here, N is the number ports), regardless of layer. At this time, in the event that a transmission is performed using only one port out of 4 ports, the transmission power is reduced to P / 4, that is, 6 dB, and there is a problem that the coverage becomes reduced. The division of the power by all the number of doors has an advantage in the cost aspect of the Tx chain of the UE, besides an advantage of battery economy of the UE. That is, when allowing power amplification, a power transmission is performed with P / 2 or P, not P / 4, for the case of 4 doors, there is a problem that the dynamic range of the transmission power of the Tx chain should become larger, which may increase the cost. On the other hand, a high-end UE can be provided with a Tx chain whose dynamic range is large, and can report it as a capacity. That is, in UL transmission, the UE can report the
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115/129 capacity in relation to whether it will transmit with a specific X dB (for example, 3 dB) or less from the maximum transmission power, and this can be considered in the determination of non-coherent standardized transmission factor. For example, in the case of grade 1 TPMI indices from 24 to 27, the normalization factor can be defined as ^ 2 _or 1 not 2, or promised / defined in advance as a specific s value (for example, ^ 2) _in advance .
[0491] In case the proposed code dictionary is used for SB TPMI, a code word used for each SB can be changed. For example, the TPMI of a specific SB can be based on the code dictionary (for example, full coherence code dictionary) that uses all ports, and another specific SB can be based on the code dictionary (for example, partial coherence codes) using part of the ports. In this case, when the number of ports is changed for each SB, there is a case where the UL power control becomes very complex. Therefore, the number of ports used in the SB can be determined with WB (this can be signaled with the dictionary format of port selection codes or the bitmap format), and it can be proposed that TPMI SB consider only the code dictionary that uses the entire number of ports indicated with WB. That is, when describing with the aspect of power scaling factor, it is assumed that the power of the TPMI that uses all the power P used in the transmission of total TPMI is normalized to 1. The port number, power scaling and / or p (0 <p <= 1) used in the transmission of TPMI from SB is determined by the method as TPMI WB, and TPMI SB is normalized as the power scaling factor 1 necessarily so as not to change the p value.
[0492] A code dictionary-based transmission to UL is supported by UL grant signaling as follows, at least:
[0493] - SRI + TPMI + TRI, here, TPMI is used to represent the pre
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116/129 preferred encoder through the SRS port of the SRS resource selected by the SRI. When a single SRS resource is defined, the SRI may not have existed. TPMI is used to indicate the preferred pro-encoder through the SRS port of the unique SRS resource that is defined.
[0494] - Indication support for a plurality of SRS resource selections [0495] In the case of a code-based transmission to UL based on CP-OFDM, the UE is configured with UL frequency selective pre-coding , and in the case where the TPMI SB signaling method, one of the following alternatives may be supported:
[0496] - Alt 1: Only for PRB allocated for a given PUSCH transmission, TPMI SB is signaled to the UE through DCI.
[0497] - Alt 2: Regardless of the actual RA for a given PUSCH transmission, TPMI SB is signaled to the UE through DCI for all PRBs in the UE.
[0498] However, other alternatives are also not excluded. In the case where the dual stage code dictionary is supported, TPMI SB can correspond to W2.
[0499] TPMI WB can be signaled together with the subband TPMI or not.
[0500] In the case of the UL code dictionary scheme, one of the following two structures can be supported in the NR.
[0501] - Alt 0: Single-stage code dictionary [0502] - Alt 1: Dual-stage code dictionary [0503] At LTE, in order to support SC-OFDM which requires a design constraint, such as maintaining PAPR and CM, we used a single-stage UL code dictionary for 2 ports and 4 ports (ie, CM should not be increased due to multi-layer transmission). Therefore, in the case where the grade is greater than 1, the LTE UL code dictionary includes zero entries for each
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117/129 code word.
[0504] However, since CP-OFDM is used for UL transmission on NR, the CM maintenance constraint may not be a core design target of the UL code dictionary. In addition, support for UL frequency-selective pre-coding for CP-OFDM has been consented. Therefore, as a design reference to solve the control channel overload problem for frequency selective UL-MIMO programming, it is natural to consider the UL dual-stage code dictionary (ie, W1W2 similar to DL).
[0505] Therefore, in the present disclosure, the dictionary structure of dual stage code (W = W1W2) for UL frequency selective precoding for at least CP-OFDM can be considered.
[0506] In the dual stage code dictionary, the final UL pre-encoder W by SB can be divided into the PMI component of WB W1 and the corresponding PMI component of SB W2. In this structure, the PMI component of WB W1 can include a beam / group of beams, and the PMI component of SB W2 can include a beam selector and / or co-phase component (for example, for X- in). In the dual-stage code dictionary, W1 can include DFT beam (s) whose performance is particularly good. This is due to the fact that the gNB is equipped with a uniformly arranged linear (or flat) antenna element / panel. Unlike TRP, the UE can be provided with an arbitrary separate antenna element / panel, and therefore, low antenna correlation can be expected. Due to this reason, the UL code dictionary of NR should be designed considering the antenna layout and structure of the UE. This means that the UL code dictionary must run well for an arbitrary UE antenna layout and structure. In this context, the DL 4Tx Household code dictionary can be considered. However, for frequency selective pre-coding, the overhead of TPMI signaling can increase from
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118/129 according to the number of configured SBs. Therefore, in order to efficiently reduce the total number of signaling overload, a Household code dictionary having a double stage structure can be considered. In this scheme, W1 can include the group of L beams (for example, L = 2, 4, L is configurable), where each beam can be selected by gNB from the Household code dictionary. N2 can perform a beam selection that requires only ' ^ο ° ² bits per SB.
[0507] This is, therefore, since the NR code dictionary of NR should be designed to perform well for an arbitrary EU antenna array and structure, the DL Household code dictionary including bundling of beams for the UL code dictionary can be considered.
[0508] If the UE is provided with multiple panels, the selection and / or combination of panels can be considered for robust transmission in the case of rapid rotation of the UE, blocking, among others. Such types of panel selection and / or combination functions can be supported by W1 or W2. In this case, the following three factors need to be considered for the UL code dictionary scheme.
[0509] · The number of panels supported in the UL code dictionary [0510] · The number of supported ports for each panel [0511] · If the UE has a different number of ports per panel [0512] The above three factors can simplified, but the code dictionary structure can still be complex. Therefore, since the antenna port of the different panels in the UE can have different mean RSRP values, SRI can be used for panel selection or antenna port group selection. This means that the antenna port of different panels can be supported independently by different features. In short, the dictionary of
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119/129 UL codes are designed assuming a single panel, and the SRI can be used for panel selection function.
[0513] In NR, an indication for multiple SRS resource selections can be supported. In the case of a plurality of SRS resources that can be indicated by the SRI field, the function of combining panels can be considered. The combination of panels plays an important role in increasing the conformation gain per beam by applying an inter-panel corrector appropriate to the phase and / or amplitude. Therefore, if several SRS features are indicated for the panel combination function, it is necessary to introduce additional TPMI for the panel broker.
[0514] That is, the UL code dictionary can be designed using a single panel, and the SRI can be used as the panel selection function. In addition, if several SRS features are indicated for the panel combination function, an additional TPMI must be introduced for the inter-panel phase / span corrector.
[0515] The SRI can indicate multiple selections of SRS resources that can support joint transmission of multiple panels on UL. In addition, each panel transmission associated with each of the indicated SRS resources can be directed to different UL reception points in the UL-CoMP context. In order to support it properly, the NR network must calculate at least the exact MCS for each of the different layer groups corresponding to different SRS resources using the separate power control process for each SRS resource. Generally, it is necessary to support a plurality of ULPC processes for the UE, and each of the ULPC processes can be associated with at least one SRS resource that is configured for the UE. For example, the configured SRS resources of ID # 1 and # 2 can be associated with the same ULPC A process, and another configured SRS resource of ID # 3 can be associated with an
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Different ULPC B. IILPC A and B processes can be directed to different reception points, and SRS # 1 and # 2 resources following the same ULPC A process can be selected dynamically by indication of SRI which is agreed upon in the UL grant. . For example, in the case where the resources of SRS # 1 (including the corresponding TPMI / TRI) and # 3 (including the corresponding TPMI / TRI) are normally indicated by the SRI field in the UL grant, for example, this can be interpreted as a joint reception operation of UL-CoMP in the transmission of multiple UL panels and gNB which is distinguished as a group of layers.
[0516] In NR, in order to apply frequency selective pre-coding for UL-MIMO, the increased control channel overhead due to the indication of the SB PMI can be a serious problem. In order to solve the problem, a level 2 DCI can be considered as one of the alternatives, an advantage and a disadvantage may be different according to the detailed factors of the level 2 DCI. In relation to the delay problem, the problem From DCI decoding failure and DCI overload, level 2 DCI of three types of versions can be discussed as follows, one by one.
Option 1:
[0517] - 1st DCI: UL grant as DCI LTE 0/4 [0518] - 2 ^ DCI: SB PMIs for allocated RBs [0519] - DCI transmission delay: 2 DCIs are transmitted in the same subframe.
Option 2:
[0520] - 1st DCI: SB PMIs for all RBs [0521] - 2 ^ DCI: UL grant as DCI LTE 0/4 [0522] - DCI transmission delay: one or more 2 ² DCIs referring to à 1 ^â DCI is transmitted in / after the U DCI transmission subframe.
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121/129 [0523] With respect to the channel aging issue, Option 2 may not be desirable, since UL grant information can be distributed several subframes after the distribution of SB PMIs. The motivation for introducing such frequency-selective UL pre-encoders is to achieve the precise UL link adaptation by also exploring the frequency domain, so that it is desired that the complete set of programming information be distributed instantly to the UE when it is scheduled for UL transmission. For Option 1, there is no latency problem, as 2 DCIs are transmitted in the same subframe.
[0524] For all options, the complete information about UL programming is divided into two DCIs, so that it appears that the UE cannot transmit UL data in case it fails to decode one of the two DCIs. For Option 2, in case the UE fails to decode at 1 ^ DCI, several 2 ^ DCIs referring to 1 ^ DCI can be wasted. To address this issue, an appropriate mechanism for reporting 1- DCI decoding results to gNB may be required.
[0525] In terms of DCI overhead, these two options help to reduce overhead. For Option 1, the PMIs of SB only for programmed SBs, not for all SBs, are indicated by the 2 ^ DCI so that, in the case of small RBs being allocated to the 2 ^ EU DCI, the payload size be reduced adaptively. For Option 2, the SB PMIs for all SBs should be indicated through 1 ^ DCI, since 2 ^ DCI including the UL grant may be signaled after the first transmission of DCI. In this scheme, overload savings can be achieved over time. In other words, the 1st DCI is transmitted only once for multiple UL granting so that the DCI overhead is saved.
[0526] The other option is the single level DCI as follows:
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Option 3:
[0527] - Single DCI: SB PMI (s) for allocated RB (s) and UL grant as DCI LTE 0/4 [0528] Option 4:
[0529] - Single DCI: SB PMI (s) for all RB (s) allocated and UL grant as DCI LTE 0/4 [0530] In Options 3 and 4, there are no aging problems channel or decoding failure that the level 2 DC has, but may need to contain more payload in a single DCI. Even in Option 3, it is desirable to maintain the same payload size regardless of the RB size allocated so as not to increase the DCI's BD overhead. As a result, the DCI size for option 3 is decided based on the case when the allocated RB is broadband and the DCI size for options 3 and 4 is the same.
[0531] In order to minimize the overload of DCI, the compression for indication of PMI of SB is crucial. To resolve the control channel overload issue for frequency-selective UL-MIMO programming, a compression method for SB PMI payload should be investigated along with the code dictionary structure. In the double-code dictionary structure, one final UL pre-encoder W per subband can be decomposed into a broadband PMI component W1 and the corresponding subband PMI component W2. Therefore, the UL programming DCI contains a W1 broadband and multiple W2 SBs. In order to reduce the payload size of the SB W2, code dictionary subsampling can be considered. In the case of the unique code dictionary structure like the Rel-8 LTE code dictionary, the SB PMI payload can also be compressed in a similar way. More specifically, the code dictionary subset for SB PMI is constrained based on WB PMI in such a way that the subset includes highly PMIs
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123/129 correlated with WB PMI.
[0532] The UL DCI scheme for frequency selective programming should be investigated in terms of latency problems, DCI decoding failure problems, and DCI overload. In addition, in order to reduce the DCI overhead, the SB PMI should be indicated from a subset of the entire code dictionary.
[0533] FIG. 17 is a flow chart illustrating the PUSCH transmission operation of a UE in accordance with an embodiment of the present invention. In relation to this flowchart, the description / modalities described above can be applied in an identical / similar way, and the repeated description will be omitted.
[0534] First, a UE can receive DCI for UL transmission scheduling (step S1710). At this time, the DCI may include TPMI as pre-coding information, which is information from a pre-coding matrix index selected for PUSCH transmission from the UE. In addition, the DCI can additionally include RI, which is the layer information used for PUSCH transmission from the UE, in which case the RI can be coded together with the TPMI and included in the DCI. In addition, in order to decide the DMRS port, a predefined DMRS field / table size (in the DCI) can be decided differently according to the IR that is coded together with the TPMI. That is, the DMRS field / table can be encoded / decoded / interpreted / defined / configured differently based on / in accordance with IR.
[0535] As a modality, the TPMI is indicated for the SRS resource configured for the UE, and the IR can normally be indicated for the configured SRS resources. Alternatively, as another example, TPMI and RI can generally be indicated for all SRS resources configured for the UE. Alternatively, in another modality, TPMI and RI can be indicated for each SRS resource configured for the UE.
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124/129 [0536] The UE can then perform PUSCH transmission based on a code dictionary based on pre-coding information (step S1720). At this time, in the case where PUSCH is transmitted using four antenna ports, the code dictionary may include a first group including non-coherent pre-coding arrays to select only one port for each layer, a second group including arrays of partial coherence pre-coding for selecting two ports in at least one layer and / or a third group including full coherence pre-coding matrices for selecting all ports for each layer. Here, the non-coherent pre-coding matrix can represent a matrix including a vector having a non-zero value in each column, the partial coherent pre-coding matrix can represent a matrix including two vectors with a non-zero value in at least minus one column, and the full coherence precoding matrix can represent a matrix including only vectors with a non-zero value. In addition, the code dictionary can be a code dictionary based on a CPOFDM waveform.
[0537] In addition, although not shown in the flowchart, the UE can receive restriction information on the number of layers used in PUSCH transmission. For example, the UE can receive restriction information on the maximum number of layers usable in transmitting PUSCH from gNB via upper layer signaling (e.g., RRC). In this case, the UE does not use the code dictionary corresponding to the restricted layer in the PUSCH transmission. In addition, based on the restriction information on the number of layers, the size of a field in which TPMI and RI are coded together.
[0538] In addition, although not shown in the flowchart, the UE can receive restriction information from the pre-coding matrix usable in PUSCH transmission in the code dictionary. At this point, information from
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125/129 restriction of the pre-coding matrix can be flagged / generated to indicate the pre-coding matrix usable in the transmission of PlISCH in the group unit (for example, the first to the third groups) or in the individual pre-coding matrix unit . Based on the restriction information from the pre-coding matrix, the size of a field in which the TPMI and the IR are coded together is determined. That is, the field / table in which TPMI and RI are encoded together can be encoded / decoded / interpreted / defined / configured differently based on / according to the restriction information of the precoding matrix.
General device to which the present invention can be applied [0539] FIG. 18 is a block diagram of a wireless communication device according to an embodiment of the present invention.
[0540] Referring to FIG. 18, a wireless communication system includes a base station (BS) (or eNB) 1810 and a plurality of terminals (or UEs) 1820 located within the coverage of eNB 1810.
[0541] eNB 1810 includes an 1811 processor, an 1812 memory, and an 1813 radiofrequency (RF) unit. The 1811 processor implements the functions, processes and / or methods proposed above. The layers of the radio interface protocols can be implemented by the 1811 processor. The 1812 memory can be connected to the 1811 processor to store various types of information to control the 1811 processor. The 1813 RF unit can be connected to the 1811 processor to transmit and / or receive a wireless signal.
[0542] The UE 1820 includes an 1821 processor, an 1822 memory, and an 1823 radio frequency (RF) unit. The 1821 processor implements the functions, processes and / or methods proposed above. The layers of radio interface protocols can be implemented by the 1821 processor. The 1822 memory can be connected to the 1821 processor to store various types of information
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126/129 to control the 1821 processor. 18 RF unit 1823 can be connected to the 1821 processor to transmit and / or receive a wireless signal.
[0543] The 1812 or 1822 memory can be present inside or outside the 1811 or 1821 processor and can be connected to the 1811 or 1821 processor through several well-known units. In addition, the eNB 1810 and / or the UE 1820 can have a single antenna or multiple antennas.
[0544] FIG. 19 is a diagram illustrating an example of an RF module of a wireless communication device to which the method proposed in the present disclosure can be applied.
[0545] In particular, FIG. 19 shows an example of an RF module that can be implemented in the Frequency Division Duplexing (FDD) system.
[0546] First, in a transmission path, the processor described above processes data to be transmitted and provides an analog output signal to the 1910 transmitter.
[0547] Inside the 1910 transmitter, the analog output signal is filtered by a 1911 low-pass filter (LPF) to remove unwanted images caused by the previous digital-to-analog (ADC) conversion, converted upwards from the band basic to RF by a 1912 ascent converter (Mixer), and amplified by a 1913 variable gain amplifier (VGA), and the amplified signal is filtered through a 1914 filter, further amplified by a 1915 power amplifier (PA) through the 1950 duplexer (s) / 1960 antenna key (s), and transmitted through a 1970 antenna.
[0548] In addition, on the receiving path, a 1970 antenna receives signals from outside and provides the received signals, which are routed through the 1960 antenna key (s) / 1950 duplexer (s) and supplied to the 1920 receiver .
[0549] Within the 1920 receiver, the received signal is amplified by a
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127/129 low-noise amplifier (LNA) 1923, filtered through a low-pass filter 1924, and converted downwards from RF to basic band by a descent converter (Mixer) 1925.
[0550] The signal converted in the downward direction is filtered by a low-pass filter (LPF) 1926, and amplified by a VGA 1927 to obtain an analog input signal, which is supplied to the processor described above.
[0551] Additionally, a 1940 local oscillator (LO) generator generates and provides LO transmit and receive signals to the upstream converter 1912 and the downstream converter 1925, respectively.
[0552] In addition, a closed loop in phase (PLL) 1930 can receive control information from the processor and provide control signals to the LO 1940 generator to generate the transmit and receive LO signals at the appropriate frequencies.
[0553] The circuits illustrated in FIG. 19 can be arranged differently from the configuration illustrated in FIG. 19.
[0554] FIG. 20 is a diagram illustrating another example of an RF module of a wireless communication device to which the method proposed in the present disclosure can be applied.
[0555] In particular, FIG. 20 shows an example of an RF module that can be implemented in the Time Division Duplexing (FDD) system.
[0556] The 2010 transmitter and receiver 2031 of the RF module in the TDD system are the same as the structures of the transmitter and receiver of the RF module in the FDD system.
[0557] From now on, only the structure of the RF module of the TDD system is described, which is different from the RF module of the FDD system, and the same structure is mentioned in the description of FIG. 10.
[0558] The signal amplified by a 2015 power amplifier (PA) of a
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128/129 transmitter is routed through a 2050 band selection key, a 2060 bandpass filter (BPG) and one or more 2070 antenna keys, and transmitted via a 2080 antenna.
[0559] In addition, on the receiving path, the 2080 antenna receives signals from outside and provides the received signals, which are routed through the 2080 antenna key (s), the 2060 bandpass filter (GMP) and of the 2050 range selection switch, and supplied to receiver 2020
[0560] The aforementioned modalities are obtained by combining the elements and structural aspects of the present invention in a predetermined way. Each of the elements or structural aspects must be considered selectively, unless separate indication to the contrary. Each of the structural elements or aspects can be realized without being combined with other structural elements or aspects. In addition, some elements and / or structural aspects can be combined together to form the modalities of the present invention. The order of operations described in the modalities of the present invention can be changed. Some structural elements or aspects of one modality can be included in another modality, or they can be replaced by corresponding structural elements or aspects of another modality. Furthermore, it is apparent that some claims related to specific claims may be combined with other claims related to other claims in addition to the specific claims in order to constitute the modality or to add new claims by way of amendment after filing this application.
[0561] In the present disclosure, "A and / or B" can be interpreted to mean at least one of A and / or B.
[0562] The modalities of the present invention can be achieved by various means, for example, hardware, firmware, software or a combination of
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129/129 same. In a hardware configuration, methods according to the modalities of the present invention can be achieved by one or more ASICs (Integrated Circuits of Specific Application), DSPs (Digital Signal Processors), DSPDs (Digital Signal Processing Devices), PLDs (Programmable Logic Devices), FPGAs (Field Programmable Gate Arrays), processors, controllers, microcontrollers, microprocessors, etc.
[0563] In a firmware or software configuration, the modalities of the present invention can be implemented in the form of a module, or procedure, a function, etc. The software code can be stored in memory and run by the processor. The memory can be located inside or outside the processor and can transmit data and receive data from the processor through several known means.
[0564] It will be evident to those skilled in the art the possibility of making various modifications and variations in the present invention without departing from its essence or scope. Therefore, it is intended that the present invention covers the modifications and variations of this invention, as long as they are within the scope of the appended claims and their equivalents.
[Mode for the Invention] [0565] Various forms for modalities of the invention have been described in the Best Mode for the Invention.
[Industrial Applicability] [0566] The present invention, applied to the LTE / LTE-A / 5G 3GPP system, is described primarily as an example, but can be applied to several wireless communication systems in addition to the LTE / LTE-A / 5G 3GPP.

权利要求:
Claims (15)
[1]
1. Method for transmission based on the code dictionary of a Shared Physical Channel of Uplink, PUSCH, in a wireless communication system, the method performed in a User Equipment, UE (1820), FEATURED for understanding:
receiving degree restriction information from a network node (1810);
receive, from the network node, downlink control information, DCI, for PUSCH transmission;
selecting a precoder based on a DCI bit field and the received degree constraint information; and perform PUSCH transmission using the pre-encoder.
[2]
2. Method, according to claim 1, CHARACTERIZED by the fact that the degree restriction information is received from the network node (1810) with code dictionary subset restriction information, and in which the pre- encoder is selected using the DCI bit field and received code dictionary subset constraint information and degree constraint information.
[3]
3. Method, according to claim 2, CHARACTERIZED by the fact that when the PUSCH is transmitted using four antenna ports, the pre-decoder is selected, using the DCI bit field and the dictionary subset restriction information. codes received and the degree restriction information, in a code dictionary including:
a first group including non-coherent pre-coding arrays to select only one port for each layer, a second group including partial coherent pre-coding arrays to select two ports on at least one layer, and
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2/4 a third group including pre-coding matrices for total coherence to select all ports for each of the layers.
[4]
4. Method according to claim 3,
CHARACTERIZED by the fact that non-coherent pre-coding matrices have a non-zero value in each column, in which partial coherence pre-coding matrices have two non-zero values in each column, and in which the pre-coding matrices - total coherence encoding has only non-zero values
[5]
5. Method, according to claim 4, CHARACTERIZED by the fact that the code dictionary is a code dictionary based on the Division Multiplexing waveform in Cyclic Prefix Orthogonal Frequencies, CPOFDM.
[6]
6. Method, according to any of the preceding claims, CHARACTERIZED by the fact that the DCI bit field includes a Transmitted Pre-Encoding Matrix Indicator, TPMI, which is the information of an index of the pre-encoder selected for PUSCH transmission.
[7]
7. Method, according to claim 6, CHARACTERIZED by the fact that the TPMI is encoded together with a Degree Indicator, RI, which is the information of a number of layers used in the transmission of PUSCH.
[8]
8. Method, according to claim 7, CHARACTERIZED by the fact that TPMI and RI are normally indicated for all Sounding Reference Signal, SRS resources, configured for UE (1820).
[9]
9. Method, according to claim 7, CHARACTERIZED by the fact that the TPMI and the IR are indicated for each SRS resource configured for the UE (1820).
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[10]
10. Method according to any of claims 7 to 9, CHARACTERIZED by the fact that a size of a predefined field of Demodulation Reference Signal, DMRS, in the DCI, is determined differently according to the jointly coded IR with TPMI.
[11]
11. Method according to any one of claims 7 to 10, CHARACTERIZED by the fact that a size of a field in which the TPMI and the RI are coded together is decided based on the degree restriction information.
[12]
12. Method according to any of claims 7 to 11, CHARACTERIZED by the fact that the degree restriction information is received from the network node (1810) with the code dictionary subset restriction information, and by the fact that a size of a field in which TPMI and RI are coded together is decided based on the code dictionary subset restriction information.
[13]
13. Method, according to any one of the preceding claims, CHARACTERIZED by additionally comprising:
report, to a network node (1810), the UE's ability to configure the code dictionary for PUSCH transmission, before receiving the degree restriction information.
[14]
14. Processor for User Equipment, UE, in a wireless communication system, CHARACTERIZED by the fact that the processor (1821), when coupled to a radio frequency unit, RF, (1823), from UE (1820), is configured to control the dictionary-based transmission of codes from a Shared Physical Channel of Uplink, PUSCH, according to a method according to any of the preceding claims.
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[15]
15. User equipment, UE, for transmission based on the code dictionary of a Shared Physical Channel of Uplink, PUSCH, in a wireless communication system, the UE (1820) being CHARACTERIZED for understanding:
a radio frequency unit, RF, (1823), for transmitting and receiving a radio signal; and a processor (1821) for controlling the RF unit (1823), wherein the processor (1821) is configured to carry out a method according to any one of claims 1 to 14.

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法律状态:
2021-10-19| B350| Update of information on the portal [chapter 15.35 patent gazette]|

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2021-11-16| B15K| Others concerning applications: alteration of classification|Free format text: AS CLASSIFICACOES ANTERIORES ERAM: H04B 7/0456 , H04B 7/0404 , H04L 27/26 Ipc: H04B 7/0456 (2017.01), H04B 7/0404 (2017.01), H04B |

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2021-11-23| B07A| Application suspended after technical examination (opinion) [chapter 7.1 patent gazette]|

优先权:

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